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(11) | EP 0 089 204 A2 |
| (12) | EUROPEAN PATENT APPLICATION |
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| (54) | Method and apparatus for high efficiency operation of electromechanical energy conversion devices |
| (57) A method and apparatus are disclosed for controlling the conversion of electrical
energy to mechanical energy as well as for controlling the conversion of mechanical
energy to electrical energy. In a separately excited electromechanical energy conversion
system, total system power losses are minimized by simultaneously controlling the
currents flowing in the different windings of the energy conversion device such that
these currents are related by an optimizing function. This method and apparatus are
applicable to a wide variety of electric motors and generators. As an example the
current (IF) in the separately excited field (3) may be controlled by function generator
(14) to be given by the optimisation function of the armature and shunt field currents,
function generator (14) being supplied with signals (VLAPC, VIPD) representing the external command current and the shunt field current, and in a
chopping controller also being supplied with a duty cycle signal (D). |
1. Field of the Invention
[0001] This invention relates to a method and apparatus for minimizing the loss of power in all or part of a separately excited electromechanical energy conversion system having, for example, a chopper controller, battery power supply and electromechanical energy conversion device. An electromechanical energy conversion device having n spatially fixed windings, n > 1, for producing a magnetic field, and having m movable windings, m > 1, for producing a magnetic field which opposes the magnetic field produced by the n spatially fixed windings, is separately excited if the magnetic field produced by the n spatially fixed windings can be varied, at least in part, independently of the magnetic field produced by the m movable windings. For example, in a separately excited dc motor/generator, the n spatially fixed windings can be any combination of constantly excited field windings, series field windings, and shunt field windings, with at least one separately excited field winding. The m movable windings can be armature windings.
[0002] Hereafter, unless otherwise stated, the term "field" will be used to refer to the electrical circuit of field winding(s). Also, the term "armature" will be used to refer to the electrical circuit of armature winding(s). This terminology is common in the literature.
2. Description of the Prior Art
[0003] (a) First, the conversion of electrical energy to mechanical energy in a dc motor will be considered. Heretofore, the speed and torque control of a separately excited motor, in the low speed running mode, was carried out by maintaining the field current constant and varying the armature voltage, and in the high speed running mode, by maintaining the armature voltage constant and varying the field current. This type of two speed-range controller was modified by Ohmae et al. (Reference U.S. Patent number 4,037,144) as follows:
(I) Assume that the field magnetic flux is developed in proportion to the field current IF.
(II) Assume that the field magnetic flux is independent of the armature current IA.
(III) Assume that the field circuit resistance RF is not a function of field current IF.
(IIIa) For a chopper controller, assume that RF is fixed.
(IV) Assume that the armature circuit resistance RA is not a function of armature current IA.
(IVa) For a chopper controller, assume that RA is fixed.
(V) Then the electrical power loss W=IA2·RA+IF2·RF is minimized when
(VI) Therefore, modify a two speed-range controller to maintain the relationship of
IF to IA as given in (V), unless the value of IF thus calculated exceeds minimum or maximum
limits. In the latter case, maintain IF above the minimum limit or below the maximum limit, respectively.
[0004] The maximum limit on IF is stated by Ohmae et al. to be that level of current which causes the field magnetic circuit to be saturated. For a range of IF below this limit, assumptions (I) and (II) are invalid. The reason for this is that the incremental change in the field magnetic flux caused by a change in the field current is a function of both the field current magnitude and the armature current magnitude. Assumptions (III), (IIIa), (IV) and (IVa) can also be significantly inaccurate. The present invention can achieve higher efficiency because it is not based on the above assumptions.
[0005] The implementation of (VI) by Ohmae et al, still requires a two speed-range controller. The present invention provides a simpler apparatus.
[0006] In a paper titled "Minimization of Electrical Losses in a Battery Electric Vehicle" by J. Morton, J. Jones, and C. Watson, presented at Drive Electric 80, Wembley, UK, October 16, 1980, another scheme for minimizing 12R losses in a motor system was presented. In this scheme, field flux is assumed to be represented by a second degree polynomial in field current, independent of armature current. Armature chopper duty cycle and field chopper duty cycle are controlled simultaneously as a function of accelerator pedal position and motor speed. (No algorithm for determining the appropriate values of armature chopper duty cycle and field chopper duty cycle for different accelerator pedal positions and motor speeds is given.) Since the armature chopper duty cycle and the field chopper duty cycle are controlled and not the armature current and the field current, this method depends on the relationship between chopper duty cycle and chopper current in order for the system optimization to work. One problem is that this relationship is dependent on the stability of circuit parameters which in fact can vary due to manufacturing tolerances, temperature, and component aging. In particular, the relationship of armature current to armature chopper duty cycle is very sensitive.
[0007] The present invention makes no assumptions regarding field flux as a function of field current or armature current. Furthermore, the present invention controls motor currents directly, which is a more efficacious way to minimize power loss in the system than controlling chopper duty cycles. Also, the present invention is not limited to minimizing I2R losses; all electrical losses can be minimized, such as magnetic losses, which are modelled as I 2 R losses.
[0008] (b) Second, in considering the conversion of mechanical energy to electrical energy, no prior references were found regarding power loss minimization.
Objects of the Present Invention
[0009] It is accordingly an object of the present invention to provide a method and apparatus for minimizing the loss of power in a separately excited electromechanical energy conversion device and in its controller.
[0010] It is another object of the present invention to provide a method and apparatus for minimizing total system power loss including power loss in a separately excited electromechanical energy conversion device, in its controller and in its electrical power source (for motors) or its electrical load (for generators).
[0011] Another object of the present invention is to provide this minimization both for the conversion of electrical energy to mechanical energy as well as for the conversion of mechanical energy to electrical energy.
[0012] Another object of the present invention is to provide this minimization for a wide variety of motors and generators, including devices having a shunt field as well as devices lacking a shunt field.
[0013] Viewed from one aspect, there is provided a method for minimizing, by use of a predetermined optimizing function, the loss of power in a separately excited electromechanical energy conversion device and in a controller of said energy conversion device, said energy conversion device having n spatially fixed windings, n > 1, for producing a first magnetic field, and having m movable windings, m > 1, for producing a second magnetic field which opposes said first magnetic field produced by said n spatially fixed windings, such that said first magnetic field produced by said n spatially fixed windings can be varied, at least in part, independently of said second magnetic field produced by said m movable windings, said method comprising:
the step of first generating a command signal having a magnitude A;
the step of generating currents I1(A), 12(A),...,In(A) in said n spatially fixed windings, respectively;
and the step of generating currents In+1(A), In+2(A),...,In+m(A) in said m movable windings, respectively;
wherein said currents
are selected in such a manner that their magnitudes as a function of said command
signal having a magnitude A satisfy said predetermined optimizing function;
and wherein said predetermined optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
[0014] Viewed from another aspect there is provided an apparatus for minimizing, by use of a predetermined optimizing function, the loss of power in a separately excited electromechanical energy conversion device and in a controller of said energy conversion device, said energy conversion device having n spatially fixed windings, n > 1, for producing a first magnetic field, and having m movable windings, m > 1, for producing a second magnetic field which opposes said first magnetic field produced by said n spatially fixed windings, such that said first magnetic field produced by said n spatially fixed windings can be varied, at least in part, independently of said second magnetic field produced by said m movable windings, said apparatus comprising:
means for first generating a command signal having a magnitude A;
means for generating currents II(A), I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A), In+2(A),...,In+m(A) in said m movable windings, respectively;
wherein said currents
are selected in such a manner that their magnitudes as a function of said command
signal having a magnitude A satisfy said predetermined optimizing function;
and wherein said predetermined optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
Brief Description of the Drawings
[0016]
Fig. 1 is a block diagram of a separately excited electromechanical energy conversion device with a "Long shunt" field;
Fig. 2 is a block diagram of a separately excited electromechanical energy conversion device with a "Short shunt" field;
Fig. 3 is a block diagram of one embodiment of the present invention;
Fig. 4 is a block diagram of another embodiment of the present invention;
Fig. 5 is a block diagram of another embodiment of the present invention;
Fig. 6 is a block diagram of another embodiment of the present invention;
Fig. 7 is a block diagram of another embodiment of the present invention;
Fig. 8 is a block diagram of another embodiment of the present invention;
Fig. 9 is a schematic of an External Command Device;
Fig. 10 is a schematic of a Function Generator;
Fig. 11 is a schematic of an Armature Controlling Circuit;
Fig. 12 is a schematic of a Field Controlling Circuit;
Fig. 13 is a schematic of an Armature Driving Circuit;
Fig. 14 is a schematic of a Field Driving Circuit;
Fig. 15 is a schematic of a forward or step down chopper control circuit; and
Fig. 16 is a schematic of a flyback or step up chopper control circuit.
The Method
[0017] The following derivation is applicable to an energy conversion device, in particular to a dc motor/generator with an armature, a permanent magnet field, a constantly excited field, a series field, a long shunt field or a short shunt field, and a separately excited field. An optimizing function fOPT is derived, wherein fOPT gives the desired relationship between the currents in the various windings of the device in order for the total power loss in the system to be minimized. For other types or other configurations of energy conversion devices, a similar derivation will produce the corresponding optimizing function fOPT. The optimizing function fOPT can be predetermined from the characteristics of the energy conversion system being optimized; or fOPT can be periodically determined by an adaptive controller that measures, directly or indirectly, any characteristics of the energy conversion system that can vary.
[0018] In applying this method, approximations of fOPT can be used, with the resulting power losses dependent upon the accuracy of the approximation. Examples of approximations of fOPT that can be used are: a power series approximation; a piecewise-linear approximation; and a sum of step functions approximation.
[0019] Furthermore, the currents in the various windings of the energy conversion device can each be a different function of the command signal that operates the controller, as long as these currents satisfy the optimizing function fOPT. That is, if the amplitude of the command signal is A, and if the current in winding i of the energy conversion device is Ii (A), where I > i > n+m, then overall power losses are minimized if I1(A). I2(A),...,In(A),In+1(A), In+2(A),...,In+m(A) satisfy the optimizing function fOPT.
[0020] Because the method of the present invention can be practiced in different ways, the drawings relating to the description of this method show only the driving circuits of the controller connected to the energy conversion device. Fig. 1 illustrates a controller connected to a device with a Long Shunt Field 1. FIG. 2 illustrates a controller connected to a device with a Short Shunt Field 2. For the energy conversion device and the controller,
where I = Shunt Field current
IA = Armature current
IF = Separately Excited Field current
IC = Constantly Excited Field current
RP = resistance of Shunt Field (1 in FIG. 1, 2 in FIG. 2)
RF = sum of resistance of Separately Excited Field (3 in FIGS. 1 and 2) and Separately Excited Field Driving Circuit (4 in FIGS.1 and 2)
RC = sum of resistance of Constantly Excited Field (5 in FIGS. 1 and 2) and Constantly Excited Field Driving Circuit (6 in FIGS.1 and 2)
[0021] RA1 and RA2 are defined differently for the Long Shunt configuration and the Short Shunt configuration:
RAl = sum of resistance of Series Field 8 and Armature 9 (FIG. 1); or
RAl = resistance of Armature 9 (FIG. 2)
RA2 = resistance of Armature Driving Circuit 10 (FIG. 1); or
RA2 = sum of resistance of Series Field 8 and Armature Driving Circuit 10 (FIG. 2)
[0022] By using these two definitions for RA1 and RA2' the following discussion applies to both the Long Shunt configuration (FIG. 1) and the Short Shunt configuration (FIG. 2), although the remaining drawings illustrate only the Long Shunt configuration.
where T = mechanical torque input or output
Ø = strength of Permanent Magnet Field (7 in FIGS.1 and 2)
Substituting IA =
into (1):
[0023] Differentiating (2) with respect to IF and setting the result equal to zero:
Substituting IA for
in (3);
fE(IP,IA,IF,IC,Ø) can be measured, for example, by performing a blocked rotor test on the energy conversion device. With IC and Ø constant, T can be measured for different values of Ip, IA, and IF. Then
[0024] Therefore, (4) can be solved numerically to give
fOPT is the optimizing function referred to previously. If the energy conversion device lacks a shunt field, then (4) becomes
where
[0027] When an armature or a field driving circuit is, in particular, a chopper, the value of that circuit's resistance becomes dependent on the chopper duty cycle. This is because the power source resistance (for motors) or the load resistance (for generators) is switched in and out by the chopper. In a system having an electromechanical energy conversion device with n + m windings, the duty cycle of the chopper circuit that drives winding i is Di, ≤ i < n + m. The following is a detailed analysis of this effect.
[0028] The schematic of a forward or step down chopper circuit is shown in FIG. 15. The load 61 can be a motor armature winding (E = back emf, E < V) or a motor field winding (E=O). When the electronic switch 62 is closed, current ISOURCE flows from the voltage source whose voltage is V. Current IMOTOR flows through the load 61, the inductor 63, and the switch 62. When the switch 62 is open, IMOTOR flows through the load 61, the inductor 63, and the freewheeling diode 64. With no filter 65, ISOURCE = IMOTOR when the switch 62 is closed, and ISOURCE = 0 when the switch 62 is open. Let
RMOTOR = the resistance of the motor/generator 61
RSWITCH = the resistance of the electronic switch 62
RINDUCTOR = the resistance of the inductor 63
RDIODE the resistance of the freewheeling diode 64
[0029] RSOURCE = the resistance of the voltage source D. = the fraction of the time that the switch 62 is on, i.e., the duty cycle of the chopper. As previously indicated, generally Di is the duty cycle for an armature chopper or a field chopper.
[0031] If the current flowing into the voltage source whose voltage is V is filtered by filter 65 so that ISOURCE is nearly constant, then
[0033] The schematic of a flyback or step up chopper circuit is shown in Figure 16. This circuit applies only to a motor armature winding, with E < V. When the electronic switch 62 is closed, current IMOTOR flows through the armature winding 61, the inductor 63, and the switch 62. When the switch 62 is open, IMOTOR flows in the armature winding 61, the inductor 63, and the freewheeling diode 64. With no filter 65, ISOURCE = IMOTOR when the switch 62 is open, and ISOURCE = 0 when the switch 62 is closed.
[0035] If the current flowing into the voltage source whose voltage is V is filtered by filter 65 so that ISOURCE is nearly constant, then ISOURCE = (1 - Di) x IMOTOR. The equivalent source resistance to IMOTOR is (1 - Di)2 x RSOURCE. Then
[0036] For an armature circuit, this dependence of circuit resistance on chopper duty cycle can be converted to an equivalent dependence of circuit resistance on motor speed. The following is a detailed analysis of this effect.
[0040] In both cases, Di is related to ω. Hereafter [D1, D2, ..., Dn+m] is referred to simply as D a multi-valued variable; also,.in defining D, ω can be substituted for any D. that is the duty cycle of a chopper driving an armature winding. In this way, the dependence of fOPT on D is made more general.
[0041] In energy conversion systems having a high power source resistance (for motors) or a high load resistance (for generators), as for example in battery powered systems, this effect is important. In such cases the function fOPT becomes dependent on the duty cycles D of the various chopper driving circuits. In practical systems, the variation of armature circuit resistance will have the predominant effect on fOPT. Therefore, in such systems, dependence of fOPT on D is reduced to a dependence on the armature chopper duty cycle, or equivalently, on W.
[0042] Another result of specifically using a chopper for a driving circuit is the presence of an ac ripple in that circuit's output current. This ac component can cause an effective change in the resistance of the motor or generator winding that it passes through. This is due to form factor 12R losses, skin effect, and magnetic losses, such as eddy currents and hysteresis. All of these physical effects can be modeled by making the effective circuit resistance a function of both dc current and ac current. Since ac current is a function of chopper duty cycle Di, fOPT is dependent on D. Thus, different loss mechanisms are modeled as 12R losses, which then allows the optimization scheme of the present invention to be applied. Since accurate modeling of motor systems using chopper controllers is difficult, the determination of equivalent resistances may have to be done entirely experimentally.
[0043] Reference: "Series Motor Parameter Variations as a Function of Frequency and Saturation", by H.B. Hamilton and Elias Strangas, IEEE PES Winter Meeting, New York, NY, February 3-8, 1980.
[0044] In fact, fOPT can be determined entirely experimentally. A motor or generator is operated at a fixed torque and speed while the separately excited field current is varied. The value of separately excited field current that minimizes the input power to the system (for a motor) or that maximizes the output power (for a generator) is the desired value at that torque and speed. Those values, along with the corresponding values of armature current for each torque and speed, are the values of fOPT.
[0045] Accordingly, the power loss minimization of the present invention is achieved for separately excited electromechanical energy conversion devices having a shunt field by controlling the separately excited field current, IF, so as to be fOPT (IA'IP), where IF = fOPT[IA,IP) is the solution to (4).
[0046] Accordingly, also, the power loss minimization of the present invention is achieved for separately excited electromechanical energy conversion devices lacking a shunt field by simultaneously controlling the armature current, IA, and the separately excited field current; TF, such that IF = fOPT(IA) or IA = fOPT-1(IF), where the latter is the solution to 5.
The Apparatus
[0047] 1. Two embodiments of the present invention for separately excited electromechanical energy conversion devices having a shunt field are described.
[0048] (a) FIG. 3 is a block diagram of one embodiment of the present invention. The External Command Device 11 generates a current command VIAPC to the Armature Controlling Circuit 12. This in turn operates the Armature Driving Circuit 10, causing the Armature 9 and the Series Field 8, in parallel with the Shunt Field 1, to have a total current equal to IA+IP flowing in them. Shunt Field current Ip is detected by the Shunt Field Current Sensor 13 which outputs signal VIPD to the Function Generator 14. The latter, which also receives VIAPC from the External Command Device, generates a current command VIFC to the Field Controlling Circuit 15, where VIFC = fOPT [(VIAPC - VIPD), VIPD]. This in turn operates the Field Driving Circuit 4, driving current IF through the Separately Excited Field 3, where IF = fOPT(IA, IP).
[0049] If the embodiment of FIG. 3 were a chopper controller, then function generator 14 would also receive a signal representing the duty cycle D, as shown in dotted lines. The effect of this would be to minimize total system power loss.
[0050] (b) FIG. 4 is a block diagram of another embodiment of the present invention. The External Command Device 11 generates a command VAC to the Armature Controlling Circuit 12. This in turn operates the Armature Driving Circuit 10. Armature current IA is detected by the Armature Current Sensor 16, which outputs signal VIAD to the Function Generator 14. Shunt Field current IP is detected by the Shunt Field Current Sensor 13, which outputs signal VIPD to the Function Generator. The latter generates a current command VIFC to the Field Controlling Circuit 15, where VIFC = fOPT(VIAD, VIPD). This in turn operates the Field Driving Circuit 4, driving current IF through the Separately Excited Field 3, where IF = fOPT(IA,Ip).
[0051] If there is no permanent magnet field and no constantly excited field in the energy conversion device, and if this embodiment is used for converting mechanical energy to electrical energy, then fOPT may have to be changed slightly to make IF non-zero when IA is zero. Otherwise, generation may not be able to start up.
[0052] If the embodiment of FIG. 4 were a chopper controller, then function generator 14 would also receive a signal representing the duty cycle D for reasons described in connection with FIG.3,
[0053] 2. Four embodiments of the present invention for separately excited electromechanical energy conversion devices lacking a shunt field are described. Before discussing these four embodiments, note that FIGS. 5-8 show the signal representing the duty cycle D should these embodiments be chopper controllers and for reasons previously described.
[0054] (a) FIG. 5 is a block diagram of another embodiment of the present invention. The External Command Device 11 generates a current command VIAC to the Armature Controlling Circuit 12. This in turn operates the Armature Driving Circuit 10, causing the Armature 9 and the Series Field 8 to have current IA flowing in them. VIAC also operates the Function Generator 14, which generates current command VIFC to the Field Controlling Circuit 15, where VIFC = fOPT(VIAC). This in turn operates the Field Driving Circuit 4, driving current IF through the Separately Excited Field 3, where IF = fOPT(IA).
[0055] (b) FIG. 6 is a block diagram of another embodiment of the present invention. The External Command Device 11 generates a command VAC to the Armature Controlling Circuit 12. This in turn operates the Armature Driving Circuit, 10. Armature current IA is detected by the Armature Current Sensor 16, which outputs signal VIAD to the Function Generator 14. The latter generates a current command VIFC to the Field Controlling Circuit 15, where VIFC = fOPT(VIAD). This in turn operates the Field Driving Circuit 4, driving current IF through the Separately Excited Field 3, where IF =fOPT(IA).
[0056] If there is no permanent magnet field and no constantly excited field in the energy conversion device, and if this embodiment is used for converting mechanical energy to electrical energy, then fOPT may have to be changed slightly to make IF non-zero when IA is zero. Otherwise, generation may not be able to start up.
[0057] (c) FIG. 7 is a block diagram of another embodiment of the present invention. The External Command Device 11 generates a current command VIFC to the Field Controlling Circuit 15. This in turn operates the Field Driving Circuit 4, driving current IF through the Separately Excited Field 3. VIFC also operates the Function Generator 14, which generates a current command VIAC to the Armature Controlling Circuit 12, where VIAC = fOPT-1(VIFC). This in turn operates the Armature Driving Circuit 10, causing the Armature 9 and the Series Field 8 to have current IA flowing in them, where IA = fOPT-1(IF).
[0058] (d) FIG. 8 is a block diagram of another embodiment of the present invention. The External Command Device 11 generates a command VFC to the Field Controlling Circuit 15. This in turn operates the Field Driving Circuit 4. Separately Excited Field current IF is detected by the Separately Excited Field Current Sensor 17, which outputs signal VIFD to the Function Generator 14. The latter generates a current command VIAC to the Armature Controlling Circuit 12, where VIAC = fOPT-1(VIFD). This in turn operates the Armature Driving Circuit 10, causing the Armature 9 and the Series Field 8 to have current IA flowing in them, where IA = fOPT -1(IF).
[0059] 3. These embodiments of the present invention are constructed with functional blocks whose implementation is known to those skilled in the art. However, for completeness, a brief description of some of the ways in which each functional block can be implemented is included. The numbers refer to FIGS. 3 through 8.
(a) The External Command Device 11 can be a voltage source, such as a variable resistor with one end grounded, the other end connected to a fixed voltage, and the center tap as the output.
(b) The Armature Controlling Circuit 12 and the Field Controlling Circuit 15 can each be implemented as a time ratio control circuit. This can be a pulse width modulator operating at a fixed frequency. It can also be a voltage to frequency converter operating with a fixed pulse width. Variable pulse width and variable frequency operation can be combined together to achieve time ratio control, also.
(c) The Armature Driving Circuit 10 and the Field Driving Circuit 4 can each be implemented by various power switching devices combined with a diode. Driven by a time ratio control circuit, the switching device is operated to be alternately on (conducting) or off (non-conducting). The diode allows current to flow in the load during the time that the switching device is off. Silicon-controlled rectifiers, power transistors, Darlington transistors, and power field effect transistors are all commonly employed in this application. For high current controllers, a parallel connection of these parts can be used to achieve the desired current handling capability.
(d) The Armature Current Sensor 16, the Shunt Field Current Sensor 13, and the Separately Excited Field Current Sensor 17 can each be implemented by a non-inductive resistor, such as those used as ampere meter shunts. Another type of device that can be used is a Hall effect current probe.
(e) The Function Generator 14 can be implemented by using one of several analog techniques. A power series approximation of fOPT or fOPT-1 can be constructed with multipliers and summing amplifiers. A piecewise-linear approximation of fOPT or fOPT-1 can be built using amplifiers and diodes. An excellent reference on this topic is the "Nonlinear Circuits Handbook" published by Analog Devices, Inc., Norwood, Massachusetts 02062, 1974, chapter 2-1.
[0060] A combination digital and analog technique can also be used. A Read Only Memory (ROM) serves as a look up table for the desired function. The ROM is addressed by the digital output of an analog to digital converter (for fOPT(IA) or fOpT-1(IF)) or converters (for fOPT(IA,IP)). The output of the ROM feeds a digital to analog converter to change the digital value of the function to analog form.
[0061] In the case of fOPT being dependent on D an analog signal proportional to D. can be obtained by low pass filtering the pulse train that drives the switch in chopper i. The previously described analog or combination analog-digital techniques can then be applied.
[0062] 4. FIGS. 9 through 14 are the schematic of a controller designed for use in an electric vehicle. This controller can drive a dc motor or it can operate the motor as a generator to recharge the vehicle's batteries (regenerative braking). Each figure of the schematic shows one functional block of FIG. 5, upon which this controller is based.
(a) FIG. 9 is the schematic of an External Command Device. The armature current command VIAC is selected by the multiplexer 18 from the analog output of either the 5 kilohm potentiometer in the accelerator pedal 19 or the 5 kilohm potentiometer in the brake pedal 20. The selection of the command source is made by the digital signal BRAKEB, which comes from a switch in the brake pedal 21. The signal SHUTDOWN turns off the controller when neither pedal is engaged or when both pedals are engaged.
(b) FIG. 10 is the schematic of a Function Generator. Armature current command VIAC is compared to two reference voltages by comparators 24 and 25. The digital outputs of the comparators control the multiplexer 26, which selects a fixed offset (through the X inputs of the multiplexer) to be added to a selected fraction of VIAC (through the Y inputs of the multiplexer). The result is the field current command VIFC. The values of the resistors are chosen to make VIFC≈fOPT(VIAC) for the particular motor being used. fOPT(VIAC) is approximated by a four section piecewise-linear function of VIAC. The first three sections are achieved by selecting resistor values to make the fractions of VIAC going into the Y inputs of the multiplexer equal to the slopes of the piecewise-linear approximation above each of the first three breakpoints, and by selecting the values of the remaining resistors to make the fixed offsets going into the X inputs of the multiplexer such that VIFC = fOPT(VIAC) at the first three breakpoints of the piecewise-linear approximation. The fourth section is a current limit region, and is reached when the +Current Limit Sense input of the Field Controlling Circuit pulse width modulator (37 in FIG. 12) receives a signal greater than +200 millivolts.
(c) FIG. 11 is the schematic of an Armature Controlling Circuit. The output of the current sensor 27 is amplified times 32 by a differential amplifier circuit whose active elements are amplifiers 28 and 29. The multiplexer 61 selects between an inverting differential amplifier circuit and a non-inverting differential amplifier circuit. This is necessary because current in the current sensor flows in one direction during accelerating and in the other direction during braking. The pulse width modulator 30 receives its current command VIAC from the External Command Device (FIG. 9) and receives a reference related to the amount of current flowing in the armature from the output of the differential amplifier circuit. The output of the pulse width modulator is low true ANDed separately with ACCELERATES and BRAKEB by OR gates 31 and 32. The resulting signals and their complements, namely PWMACCELB and PWMACCEL, and PWMBRAKEB and PWMBRAKE, operate the Armature Driving Circuit. SYNCB and C connect to the Field Controlling Circuit (FIG. 12) and synchronize the pulse width modulator in that circuit with the Armature Controlling Circuit pulse width modulator.
(d) FIG. 12 is the schematic of a Field Controlling Circuit. The output of the current sensor 35 is amplified times 32 by a differential amplifier circuit whose active element is amplifier 36. The amplifier's output provides the pulse width modulator 37 with a reference related to the amount of current flowing in the field winding. The pulse width modulator receives its current command VIFC from the Function Generator (FIG. 10). SYNCB and C originate in the Armature Controlling Circuit (FIG. ll) and synchronize the pulse width modulators 30 and 37 in the two controlling circuits. The output of the pulse width modulator 37 is PWMFIELDB. This signal and its complement, PWMFIELD, operate the field driving circuit.
(e) FIG. 13 is the schematic of an Armature Driving Circuit. In the accelerating mode, when PWMACCEL goes high transistor 39 turns on, which then turns on the high current transistor 40. When PWMACCEL is low, there is no base drive to transistor 40 from transistor 39. Also, PWMACCELB is high, turning on transistor 41, which then turns on transistor 42. The latter removes stored charge from high current transistor 40, causing it to turn off rapidly. When high current transistor 40 is off, current flowing in the armature can continue to circulate through diode 43. The result is a dc-dc converter from V+ to the motor back emf, where V+> back emf.
[0063] In the regenerative braking mode, when PWMBRAKEB goes low transistor 44 turns on, which then turns on the high current transistor 45. When PWMBRAKEB is high, there is no base drive to transistor 45 from transistor 44. Also, PWMBRAKE is low, turning on transistor 46, which then turns on transistor 47. The latter removes stored charge from high current transistor 45, causing it to turn off rapidly. When high current transistor 45 is off, current flowing in the armature can flow through diode 48 into the V+ supply. The result is a dc-dc converter from the motor back emf to V+, where V+> back emf.
[0064] This circuit is rated for 20 Amperes of armature current. For each additional 20 Amperes of current, the circuitry within the dotted line 49 must be replicated and added in parallel to that shown in FIG. 13. If this is done, then the values of the base resistors 50 and 51 for high current transistors 40 and 45, respectively, must be selected individually for each of the paralleled transistors such that they share their load equally.
[0065] (f) FIG. 14 is the schematic of a Field Driving Circuit. Its operation is identical to that of the Armature Driving Circuit in the accelerating mode.
[0066] (g) The following table gives the manufacturer and the manufacturer's part number for the integrated circuits and transistors in this controller. Two gates from the same integrated circuit together in parallel for greater drive capability is indicated by *.
[0067] The above description of embodiments of the present invention provides a general method for improving the operating efficiency of electromechanical energy conversion devices and also provides several embodiments of the invention. Controllers embodying the present invention can be used, for example, in industrial motor control, electric vehicle control (including both accelerating and regenerative braking) and the control of generators. Additional possible variations of the method and apparatus of the present invention will be evident to those skilled in the art.
the step of first generating a command signal having a magnitude A;
the step of generating currents I1(A), 12(A),...,In(A) in said n spatially fixed windings, respectively;
and the step of generating currents In+1(A), In+2(A),...,In+m(A) in said m movable windings, respectively;
wherein said currents
are selected in such a manner that their magnitudes as a function of said command
signal having a magnitude A satisfy said predetermined optimizing function;
and wherein said predetermined optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
means for first generating a command signal having a magnitude A;
means for generating currents I1(A), 12(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A), In+2(A),...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A). In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal having a magnitude A satisfy said predetermined optimizing function;
and wherein said predetermined optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
wherein said means for generating currents Il(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving said command signal A and receiving a signal representing the magnitude of current in said shunt field winding.
wherein said means for generating currents I1(A),I2(A) , ...,I (A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving a signal representing the magnitude of current in said armature windings and receiving a signal representing the magnitude of current in said shunt field winding.
wherein said means for generating currents I1(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving said command signal A.
wherein said means for generating currents I1(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving a signal representing the magnitude of current in said armature windings.
wherein said means for generating currents In+1(A), In+2(A),...,In+m(A) includes function generator means for generating said currents in the armature windings, said function generator means receiving said command signal A.
wherein said means for generating currents In+1(A), In+2(A),...,In+m(A) includes function generator means for generating said currents in the armature windings, said function generator means receiving a signal representing the magnitude of current in said separately excited field winding.
the step of first generating a command signal A;
the step of generating currents Il(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and the step of generating currents In+l(A),In+2(A),..., In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A), In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
means for first generating a command signal A;
means for generating currents I1(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A),..., In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),....In(A),In+1(A), In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said first magnetic field caused by said n currents in each of said n windings.
means for first generating a command signal A;
means for generating currents Il(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A), ...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A), In+2(A),...,In+m(A), are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said first magnetic field caused by said m currents in each of said m windings.
means for first generating a command signal A;
means for generating currents Il(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A), ...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A), In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said resistance of said n windings as a function of said n currents.
means for first generating a command signal A;
means for generating currents Il(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A), ...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A). In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said resistance of said m windings as a function of said m currents.
means for first generating a command signal A;
means for generating currents I1(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A), ...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A). In+2(A),...,In+m(A)are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said resistance of said n+m windings as a function of said n+m currents.
means for first generating a command signal A;
means for generating currents I1(A),I2(A),...,In(A) in said n spatially fixed windings, respectively;
and means for generating currents In+1(A),In+2(A), ...,In+m(A) in said m movable windings, respectively;
wherein said currents I1(A),I2(A),...,In(A),In+1(A), In+2(A),...,In+m(A) are selected in such a manner that their magnitudes as a function of said command signal A satisfy said optimizing function;
and wherein said optimizing function takes into account the incremental changes in said first and second magnetic fields caused by each of said n+m currents in each of said n+m windings.
wherein said means for generating currents I1(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving said command signal A, a signal representing the magnitude of current in said shunt field winding and a signal representing the duty cycle D.
wherein said means for generating currents I1(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving a signal representing the magnitude of current in said armature windings, a signal representing the magnitude of current in said shunt field winding and a signal representing the duty cycle D.
wherein said means for generating currents I1(A) ,I2(A) , ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving said command signal A and a signal representing the duty cycle D.
wherein said means for generating currents Il(A),I2(A), ...,In(A) includes function generator means for generating said currents in the separately excited field winding, said function generator means receiving a signal representing the magnitude of current in said armature windings and a signal representing the duty cycle D.
wherein said means for generating currents In+1(A), In+2(A),...,In+m(A) includes function generator means for generating said currents in the armature windings, said function generator means receiving said command signal A and a signal representing the duty cycle D.
wherein said means for generating currents In+1(A), In+2(A),...,In+m(A) includes function generator means for generating said currents in the armature windings, said function generator means receiving a signal representing the magnitude of current in said separately excited field winding and a signal representing the duty cycle D.