[0001] The present invention relates to a magnetically influenced current or voltage regulator
and a magnetically influenced converter for controlled connection and disconnection
together with distribution of electrical energy.
[0002] United States Patent Publication US 4210859 discloses an inductive device comprising
a magnetic core and windings for producing two or three substantially orthogonal magnetic
fields at all points within the core. The device may be utilised as an inductor or
transformer in a variety of applications.
[0003] United States Patent Publication US 2333015 discloses a variable reactance device
of the type having a magnetic core wound with one or more coils connected in series
with a load or translating device in an alternating current circuit and an auxiliary,
separately energised, exciting coil for controlling the magnetic density in the core.
[0004] United States Patent Publication US 2716736 discloses a toroidal inductance unit,
wherein the inductive reactance may be variable without altering the number of turns,
with a novel core construction.
[0005] The invention, which is a continuation of the known transductor technology, is particularly
suitable as a voltage connector, current regulator or voltage converter in several
areas of the field of power electronics. The feature which particularly characterises
the invention is that the transformative or inductive connection between the control
winding and the main winding is approximately 0 and that the inductance in the main
winding can be regulated through the current in the control winding, and furthermore
that the magnetic connection between a primary winding and a secondary winding in
a transformer configuration can be regulated through the current in the control winding.
[0006] In the field of rectification, for example, the present invention can be employed
in connection with regulation of the high-voltage input in large rectifiers, where
the advantage will be full exploitation of a diode rectifier over the entire voltage
range. For asynchronous motors, the use of the invention may be envisaged in connection
with the soft start of high-voltage motors. The invention is also suitable for use
in the field of power distribution in connection with voltage regulation of power
lines, and may be used for continuously controlled compensation of reactive power
in the network.
[0007] Even though it should not be considered limiting for the use of the device, it may,
e.g., form part of a frequency converter for converting input frequency to randomly
selected output frequency, preferably intended for operation of an asynchronous motor,
where the frequency converter's input side has a three-phase supply which by means
of its phase conductors feeds the input to at least one transformer intended for each
of the converter's three-phase outputs, and where the outputs of such a transformer
are connected via respective, selectively controllable voltage connectors, or via
additional transformer-coupled voltage connectors, in order to form one of the said
three-phase outputs.
[0008] A second application of the device is as a direct converter of DC voltage to AC voltage
whereby the AC voltage's frequency is continuously adjustable.
[0009] The use of this type of frequency converter in a subsea context, especially at great
depths, will be where the use is required of high-capacity pumps with variable speeds.
Pumping in a subsea system will typically be performed from the underwater site to
a location above water (boosting) and with water injection from the underwater site
down into the reservoir.
[0010] Variable speed engine controls are normally based on two principles; a) direct electronic
frequency-regulated converters, and b) AC-DC-AC converters with pulse-width modulation,
and with extended use of semiconductors such as thyristors and IGBT's. The latter
represents the technology widely used in industrial applications and for use on board
locomotives, etc.
[0011] Speed control has recently been introduced for motors in underwater environments.
The main challenge has been the packing and operation of such systems. In this context,
operation refers to service, maintenance, etc. Complex electronic systems generally
have to operate in controlled environments with regard to temperature and pressure.
Marine-based versions of such systems have to be encapsulated in containers filled
with nitrogen maintaining a pressure of 1 atm. On account of heat generation as a
result of heat loss in the electronics, a substantial amount of heat may be generated,
thus resulting in the need for forced air cooling. This is usually solved by the use
of fans. The fans introduce a component which dramatically reduces the working life
of the system and represents a highly unsuitable solution.
[0012] The sensitivity of the electronics and the electronic power semiconductors is high
and requires protective circuits. This complicates the system and forces up the costs.
[0013] At great depths (over 300 metres) a protective container for such a system will be
extremely heavy, representing a fairly significant proportion of the total weight
of the system. In addition, maintenance of a system more often than not will require
the entire frequency converter to be raised, since even simpler maintenance is difficult
to perform with a remotely operated vehicle (ROV).
[0014] Thus it has been a co-ordinate object of the device according to the present invention
to offer the possibility of providing a frequency converter which is suitable for
underwater pumping operations, particularly with the focus on operational reliability,
stability and minimum maintenance requirements. The operational requirement will be
approximately 25 years at 3000 m depth.
[0015] The standard frequency converters which are based on semiconductor technology convert
alternating current (AC) power with a given frequency to alternating current power
in the other selected frequency without any intermediate DC connection. The conversion
is carried out by forming a connection between given input and output terminals during
controlled time intervals. An output voltage wave with an output frequency F0 is generated
by sequentially connecting selected segments of the voltage waves on the AC input
source with the input frequency F1 to the terminals. Such frequency converters exist
in the form of the standard symmetrical cycloconverter circuits for supplying power
from a three-phase network to a three-phase motor. The standard cycloconverter module
consists of a dual converter in each motor phase. Thus the normal method is to employ
three identical, essentially independent dual converters which provide a three-phase
output.
[0016] Amongst other known types of frequency converters is a symmetrical 12-pulse centre
cycloconverter consisting of three identical 4-quadrant 12-pulse centre converters,
with one for each output phase. All three converters share common secondary windings
on the input transformer. The neutral conductor can be omitted for a balanced 3-phase
loaded Y-coupled motor.
[0017] Another known frequency converter based on semiconductor technology is the so-called
symmetrical 12-pulse bridge circuit which has three identical 4-quadrant 12-pulse
bridge converters with one for each output phase. The input terminals on each of the
six individual 6-pulse converters are fed from separate secondary windings on the
input transformer. It should be noted that it is not permitted to use the same secondary
winding for more than one converter. This is due to the fact that each 12-pulse converter
in itself requires two completely insulated transformer secondary windings.
[0018] It has therefore been a secondary, but nevertheless essential object of the invention
to avoid primarily semiconductor components in the frequency converter which has to
be located at great depths and for this purpose the use has therefore been proposed
according to the invention of the new magnetic converter technology based on an entirely
untraditional concept.
[0019] Thus, an embodiment not according to the invention comprises a magnetically influenced
current or voltage regulator, which may be characterized in that it comprises: a body
which is composed of a magnetisable material and provides a closed, magnetic circuit,
at least one first electrical conductor wound round the body along at least a part
of the closed circuit for at least one turn which forms a first main winding, at least
one second electrical conductor wound around the body along at least a part of the
closed circuit to at least one turn which forms a second main winding or control winding,
where the winding axis for the turn or turns in the main winding is at right angles
to the winding axis for the turn or turns in the control winding. The object of this
is to provide orthogonal magnetic fields in the body and thereby control the behaviour
of the magnetisable material relative to the field in the main winding by means of
the field in the control winding. In a preferred version of this embodiment, the axis
for the turn(s) in the main winding is parallel to or coincident with the body's longitudinal
direction, while the tum(s) in the control winding extend substantially along the
magnetisable body and the axis for the control winding is therefore at right angles
to the body's longitudinal direction. A second possible variant of this embodiment
consists in the axis for the tum(s) in the control winding being parallel to or coincident
with the body's longitudinal direction, while the turn(s) in the main winding extend
substantially along the magnetisable body and the axis for the main winding is therefore
at right angles to the body's longitudinal direction.
[0020] The above embodiment can be adapted for use as a transformer by being equipped with
a third electrical conductor wound around the body along at least a part of the closed
circuit for at least one turn, forming a third main winding, the winding axis for
the turn or turns in the third main winding coinciding with or being parallel to the
winding axis for the turn or turns in the first main winding, thus providing a transformer
effect between the first and the third main windings when at least one of them is
excited. A second possibility for adapting this embodiment for use as a transformer
is to equip it with a third electrical conductor wound around the body along at least
a part of the closed circuit for at least one turn, forming a third main winding,
the winding axis for the turn or turns in the third main winding being coincident
with or parallel to the winding axis for the turn or turns in the control winding,
thus providing a transformer effect between the third main winding and the control
winding when at least one of them is excited.
[0021] Another embodiment not according to the invention comprises a magnetically influenced
current or voltage regulator, characterized in that it comprises a first body and
a second body, each of which is composed of a magnetisable material which provides
a closed, magnetic circuit, the said bodies being juxtaposed, at least one first electrical
conductor wound along at least a part of the closed circuit for at least one turn
which forms a first main winding, at least one second electrical conductor wound around
at least a part of the first and/or second body for at least one turn which forms
a second main winding or control winding, where the winding axis for the turn or turns
in the main winding is at right angles to the winding axis for the turn or turns in
the control winding. The object of this is to provide orthogonal magnetic fields in
the body and thereby control the behaviour of the magnetisable material relative to
the field in the main winding by means of the field in the control winding. The main
and control windings may of course be interchanged, thus providing a magnetically
influenced current or voltage regulator, characterized in that it comprises at least
one first electrical conductor wound round at least a part of the first and/or the
second body for at least one turn which forms a first main winding, at least one second
electrical conductor wound along at least a part of the closed circuit for at least
one turn which forms a second main winding or control winding, where the winding axis
for the turn or turns in the main winding is at right angles to the winding axis for
the turn or turns in the control winding with the object of providing orthogonal magnetic
fields in the body and thereby controlling the behaviour of the magnetisable material
relative to the field in the main winding by means of the field in the control winding.
[0022] A preferred variant of the above embodiment comprises first and second magnetic field
connectors which together with the bodies form the closed magnetic circuit.
[0023] The above embodiment can also be adapted for use as a transformer by equipping it
with a third electrical conductor wound for one turn which forms a third main winding,
the winding axis for the turn or turns in the third main winding being coincident
with or parallel to the winding axis A2 for the turn or turns in the first main winding
or in the control winding, thus providing a transformer effect between the third main
winding and the first main winding or the control winding when at least one of this
is excited.
[0024] In a preferred version of the above embodiment, the first and the second body are
tubular, thus enabling the first conductor or the second conductor to extend through
the first and the second body. In this version the magnetic field connectors preferably
comprise apertures for the conductors. In a more preferred version, each magnetic
field connector comprises a gap to facilitate the insertion of the first or the second
conductor. In an even more preferred version, the device is equipped with an insulating
film placed between the end surfaces of the tubes and the magnetic field connectors
with the object of insulating the connecting surfaces from each other in order to
prevent induced eddy currents from being produced in the connecting surfaces by short-circuitirig
of the layer of film. For a core made of ferrite or compressed powder, an insulation
film will not be necessary. Furthermore, it is particularly advantageous that each
tube in the above embodiment not according to the invention comprises two or more
core parts and that in addition an insulating layer is provided between the core parts.
The tubes in the above embodiment not according to the invention, moreover, may have
circular, square, rectangular, triangular or hexagonal cross sections.
[0025] An embodiment of the invention relates to a magnetically influenced current or voltage
regulator, characterized in that it comprises a first, external tubular body and a
second, internal tubular body, each of which is composed of a magnetisable material
and provides a closed, magnetic circuit, the said bodies being concentric relative
to each other and thus having a common axis, at least one first electrical conductor
wound round the tubular bodies for at least one turn which forms a first main winding,
at least one second electrical conductor provided in the space between the bodies
and wound around the bodies' common axis for at least one turn which forms a second
main winding or control winding, where the winding axis for the turn or turns in the
main winding is at right angles to the winding axis for the turn or turns in the control
winding. The object again is to provide orthogonal magnetic fields in the bodies and
thereby control the behaviour of the magnetisable material relative to the field in
the main winding by means of the field in the control winding. The main winding and
the control winding will also be interchangeable in this embodiment of the invention,
thus providing a magnetically influenced current or voltage regulator, where at least
one first electrical conductor is provided in the space between the bodies and wound
round the bodies' common axis for at least one turn which forms a first main winding,
at least one second electrical conductor is wound around the tubular bodies for at
least one turn which forms a second main winding or control winding, and the winding
axis for the turn or turns in the main winding is at right angles to the winding axis
for the turn or turns in the control winding.
[0026] A preferred variant of the above embodiment of the invention comprises first and
second magnetic field connectors which together with the bodies form the closed magnetic
circuit.
[0027] The above embodiment of the invention can also be adapted for use as a transformer
by equipping the device with a third electrical conductor wound for at least one turn
which forms a third main winding. In this case too the winding axis for the turn or
turns in the third main winding may either be coincident with or parallel to the winding
axis for the turn or turns in the first main winding, thus providing a transformer
effect between the first and the third main windings when at least one of this is
excited, or the winding axis for the turn or turns in the third main winding may be
coincident with or parallel to the winding axis for the turn or turns in the control
winding, thus providing a transformer effect between the third main winding and the
control winding when at least one of this is excited.
[0028] Another embodiment of the invention relates to a magnetically influenced current
or voltage regulator, comprising a first external tubular body and a second internal
tubular body each of which is composed of a magnetisable material and provides a magnetic
circuit, the said bodies being concentric relative to each other and thus having a
common axis, at least one first electrical conductor wound round the tubular bodies
for at least one turn forming a first main winding and at least one second electrical
conductor provided in a gap between the bodies and wound around the body's common
axis for at least one turn forming a second main winding or control winding, or at
least one first electrical conductor provided in a gap between the bodies and wound
around the body's common axis for at least one turn forming a first main winding and
at least one second electrical conductor wound round the tubular bodies for at least
one turn forming a second main winding or control winding, where the winding axis
for the turn or turns in the main winding is at right angles to the winding axis for
the turn or turns in the control winding with the object of providing orthogonal magnetic
fields respectively in the bodies and thereby controlling the behaviour of the magnetisable
material relative to the field in the main winding by means of the field in the control
winding, characterised in that the first and second bodies are made of a wound foil
of magnetic material, and that the regulator provides a closed magnetic circuit for
the orthogonal magnetic fields by means of said first and second bodies, a first magnetic
field connector and a second magnetic field connector, said first and second magnetic
field connectors magnetically interconnecting the respective end surfaces of the first
and second bodies.
[0029] The object again is to provide orthogonal magnetic fields in the body and thereby
control the behaviour of the magnetisable material relative to the field in the main
winding by means of the field in the control winding. In the same way as in the second-mentioned
embodiment not according to the invention, the main winding and the control winding
may be interchangeable, thus providing a device where at least one first electrical
conductor is provided in the space between the first and the second bodies and wound
round the bodies' common axis for at least one turn which forms a second main winding
or control winding, at least one second electrical conductor is wound around the tubular
bodies for at least one turn which forms a second main winding or control winding.
[0030] The invention comprises first and second magnetic field connectors which together
with the bodies form the closed magnetic circuit.
[0031] This embodiment of the device can be adapted for use as a transformer by equipping
it with a third electrical conductor wound around the external core for one turn which
forms a third main winding. In this case too there will be two alternatives: one where
the winding axis for the turn or turns in the third main winding is coincident with
or parallel to the winding axis for the turn or turns in the first main winding, thus
providing a transformer effect between the first and the third main windings when
at least one of this is excited, and one where the winding axis for the turn or turns
in the third main winding is coincident with or parallel to the winding axis for the
turn or turns in the control winding, thus providing a transformer effect between
the third main winding and the control winding when at least one of this is excited.
[0032] It is, of course, possible to implement the above embodiment of the invention in
such a manner that the two tubular bodies which form the internal core are mounted
on the outside of the tubular body forming the external core, thus providing an internal
core with one tubular body and an external core with two tubular bodies.
[0033] In a preferred variant of this embodiment of the invention, the device is characterized
in that the external core consists of several annular parts, and that the first and/or
the third main winding forms individual windings around each annular part. A second
possibility is that the control winding and/or the third main winding form individual
windings around each annular part.
[0034] The above embodiment will be the one which will be preferred in principle.
[0035] Devices according to the invention will have many interesting applications, of which
we shall mention only a few. These are: a) as a component in a frequency converter
for converting input frequency to randomly selected output frequency preferably intended
for operation of an asynchronous motor, in a cycloconverter connection, b) as a connector
in a frequency converter for converting input frequency to randomly selected output
frequency and intended for operation of an asynchronous motor, for addition of parts
of the phase voltage generated from a 6 or 12-pulse transformer to each motor phase,
c) as a DC to AC converter which converts DC voltage/current to an AC voltage/current
of randomly selected output frequency, d) as in c) but where three such variable inductance
voltage converters are interconnected in order to generate a three-phase voltage with
randomly selected output frequency which is connected to the said asynchronous machine,
e) for converting AC voltage to DC voltage within the processing industry, where the
device is used as a reluctance-controlled variable transformer where the output voltage
is proportional to the reluctance change in a core which is magnetically connected
in parallel or in series to an external or internal core with a separate secondary
winding, and where three or more such reluctance-controlled transformers are connected
to the known three-phase rectifier connections for 6 or 12-pulse rectifier connections
for diode output stage, 1) for use in a rectifier for converting AC voltage to DC
voltage for use in the processing industry, where the device forms voltage connectors
which are used as variable inductances in series with primary windings on known transformer
connectors, and where three or more such transformers are connected to three-phase
rectifier connectors for 6 or 12-pulse rectifier connectors for diode output stage,
g) for AC/DC or DC/AC converters for use in the field of switched power supply, for
reduction of the size of the magnetic voltage converter, where the device forms a
reluctance-controlled variable transformer where the output voltage is proportional
to the reluctance change in a core which is magnetically connected in parallel or
in series to an external or internal core with a separate secondary winding, preferably
by filters in which inductance is included being formed with a variable inductance,
h) as a component in a controllable voltage compensator in the high voltage distribution
network, where the device forms a linear variable inductance, i) as a component in
a controllable reactive power compensator (VAR compensator), where the device creates
linear variable inductance in connection with known filter circuits in which at least
one condenser also forms an element, the device in the form of a reluctance-controlled
transformer being employed as an element in a compensator connection where capacitance
or inductance are automatically connected and adjusted to the extent required to compensate
for the reactive power, j) in a system for reluctance-controlled direct conversion
of an AC voltage to a DC voltage, k) in a system for reluctance-controlled direct
conversion of a DC voltage to an AC voltage.
[0036] The voltage connector is without movable parts for absorbing electrical voltage between
a generator and a load. The function of the connector is to be able to control the
voltage between the generator and the load from 0-100% by means of a small control
current. A second function will be as a pure voltage switch or as a current regulator.
A further function could be forming and converting of a voltage curve.
[0037] The new technology according to the invention will be able to be used for upgrading
existing diode rectifiers where there is a need for regulation. In connection with
12-pulse or 24-pulse rectifier systems, it will be possible to balance voltages in
the system in a simple manner while having controllable diode rectification from 0-100%.
[0038] The current or voltage regulator according to the invention is implemented in the
form of a magnetic connector substantially without movable parts, and it will be able
to be used for connecting and thereby transferring electrical energy between a generator
and a load. The function of the magnetic connector is to be capable of closing and
opening an electrical circuit.
[0039] The connector will therefore act in a different way to a transductor where the transformer
principle is employed in order to saturate the core. The present connector controls
the working voltage by bringing the main core with a main winding in and out of saturation
by means of a control winding. The connector has no noticeable transformative or inductive
connection between the control winding and the main winding (in contrast to a transductor),
i.e. no noticeable common flux is produced for the control winding and the main winding.
[0040] This new magnetically controlled connector technology will be capable of replacing
semiconductors such as GTO's in high-powered applications, and MosFet or IGBT in other
applications, except that it will be limited to applications which can withstand stray
currents which are produced by the main winding's magnetisation no-load current. As
mentioned in the introduction, the new converter will be particularly suitable for
realising a frequency converter which converts alternating current power with a given
frequency to alternating current power which has a different selected output frequency.
No intermediate DC connection will be necessary in this case.
[0041] As mentioned at the beginning, devices according to the invention are capable of
being employed in connection with frequency converters, such as those based on the
cycloconverter principle, but also frequency converters based on 12-pulse bridge converters,
or by direct conversion of DC voltage to AC voltage of variable frequency.
[0042] The principle of devices according to the invention, in which a variable reluctance
is employed in a magnetisable body or main core, is based on the fact that magnetisation
current in a main winding, which is wound round a main core, is limited by the flux
resistance according to Faraday's Law. The flux which has to be established in order
to generate counter-induced voltage is dependent on the flux resistance in the magnetic
core. The magnitude of the magnetisation current is determined by the amount of flux
which has to be established in order to balance applied voltage.
[0043] The flux resistance in a coil where the core is air is of the order of 1.000 - 900.000
times greater than for a winding which is wound round a core of ferromagnetic material.
In the case of low flux resistance (iron core) little current is required to establish
a flux which is necessary to generate a bucking voltage to the applied voltage, according
to Faraday's Law. In the case of high flux resistance (air core) a large current is
required in order to establish the flux necessary to generate the same induced bucking
voltage.
[0044] By controlling the flux resistance, the magnetisation current or the load current
in the circuit can be controlled. In order to control the flux resistance, according
to the invention a saturation of the main core is employed by means of a control flux
which is orthogonal relative to the flux generated by the main winding. As already
mentioned, the above-mentioned principle forms the basis of the invention, which relates
to a magnetically influenced current or voltage regulator (connector) and a magnetically
influenced converter device.
[0045] It will be appreciated that both the connector and the converter can be produced
by means of suitable production equipment for toroidal cores. From the technical point
of view, the converter can be produced by magnetic material such as electroplating
being wound up in suitably designed cylindrical cores or used for higher frequencies
with compressed powder or ferrite. It is, of course, also advantageous to produce
ferrite cores or compressed powder cores according to the dictates of the application.
[0046] The invention will now be described in greater detail with reference to the attached
drawings, in which:
Figs. 1 and 2 illustrate the basic principle of an embodiment not according the invention.
Fig. 3 is a schematic illustration of a device that is not according to the invention.
Fig. 4 illustrates the areas of the different magnetic fluxes which form part of the
device that is not according to the invention.
Fig. 5 illustrates a first equivalent circuit for the device that is not according
to the invention.
Fig. 6 is a simplified block diagram of the device that is not according to the invention.
Fig. 7 is a diagram of flux versus current.
Figs. 8 and 9 illustrate magnetisation curves and domains for the magnetic material
in the device that is not according to the invention.
Fig. 10 illustrates flux densities for the main and control windings.
Fig. 11 illustrates a second embodiment not according to the invention.
Fig. 12 illustrates the second embodiment that is not according to the invention.
Figs. 13 and 14 illustrate the second embodiment that is not according to the invention,
in section.
Figs. 15-18 illustrate different variants, that are not according to the invention,
of the magnetic field connectors in the said second embodiment that is not according
to the invention.
Figs. 19-32 illustrate different variants, that are not according to the invention,
of the tubular bodies in the second embodiment that is not according to the invention.
Figs. 33-38 illustrate different aspects of the magnetic field connectors for use
in the second embodiment that is not according to the invention.
Fig. 39 illustrates an assembled device according to the second embodiment that is
not according to the invention.
Figs. 40 and 41 are a section and a view of an embodiment according to the invention.
Figs. 42, 43 and 44 illustrate special variants of magnetic field connectors for use
in the embodiment according to the invention.
Fig. 45 illustrates the embodiment according to the invention adapted for use as a
transformer.
Figs. 46 and 47 are a section and a view of another embodiment of the invention for
use as a reluctance-controlled, flux-connected transformer.
Figs. 48 and 49 illustrate a device not according to the invention adapted to suit
a powder-based magnetic material, and thereby without magnetic field connectors.
Figs. 50 and 51 are sections along lines VI-VI and V-V in figure 48.
Figs. 52 and 53 illustrate a core adapted to suit a powder-based magnetic material,
and thereby without magnetic field connectors, not according to the invention.
Fig. 54 is an "X-ray picture" of a variant of the other embodiment of the invention.
Fig. 55 illustrates a second variant of the device according to the second embodiment
that is not according to the invention together with the principle behind a possibility
for transformer connection.
Fig. 56 illustrates a proposal for an electro-technical schematic symbol for the voltage
connector that is not according to the invention.
Fig. 57 illustrates a proposal for a block schematic symbol for the voltage connector
that is not according to the invention.
Fig. 58 illustrates a magnetic circuit where the control winding and control flux
are not included.
Figs. 59 and 60 illustrate proposals for electro-technical schematic symbols for the
voltage converter that is not according to the invention.
Fig. 61 illustrates the use of the invention in an alternating current circuit.
Fig. 62 illustrates the use of the invention in a three-phase system.
Fig. 63 illustrates a use as a variable choke in DC-DC converters.
Fig. 64 illustrates a use as a variable choke in a filter together with condensers.
Fig. 65 illustrates a simplified reluctance model for the device according to the
invention and a simplified electrical equivalent diagram for the connector according
to the invention.
Fig. 66 illustrates the connection for a magnetic switch.
Fig. 67 illustrates examples of a three-phase use of the invention.
Fig. 68 illustrates the device employed as a switch.
Fig. 69 illustrates a circuit comprising 6 devices according to the invention.
Fig. 70 illustrates the use of the device according to the invention as a DC-AC converter.
Fig. 71 illustrates a use of the device according to the invention as an AC-DC converter.
[0047] A device not according to the invention will now be explained in principle in connection
with Figs. 1a and 1b.
[0048] In the entire description, the arrows associated with magnetic field and flux will
substantially indicate the directions thereof within the magnetic material. The arrows
are drawn on the outside for the sake of clarity.
[0049] Figure 1a illustrates a device comprising a body 1 of a magnetisable material which
forms a closed magnetic circuit. This magnetisable body or core 1 may be annular or
of another suitable shape. Round the body 1 is wound a first main winding 2, and the
direction of the magnetic field H1 (corresponding to the direction of the flux density
B1) which will be created when the main winding 2 is excited will follow the magnetic
circuit. The main winding 2 corresponds to a winding in an ordinary transformer. In
a variant, the device includes a second main winding 3 which in the same way as the
main winding 2 is wound round the magnetisable body 1 and which will thereby provide
a magnetic field which extends substantially along the body 1 (i.e. parallel to H1,
B1). The device finally includes a third main winding 4 which, in a preferred variant,
extends internally along the magnetic body 1. The magnetic field H2 (and thus the
magnetic flux density B2) which is created when the third main winding 4 is excited
will have a direction which is at right angles to the direction of the fields in the
first and the second main winding (direction of H1, B1). The device may also include
a fourth main winding 5 which is wound round a leg of the body 1. When the fourth
main winding 5 is excited, it will produce a magnetic field with a direction which
is at right angles both to the field in the first (H1), the second and the third main
winding (H2) (figure 3). This will naturally require the use of a closed magnetic
circuit for the field which is created by the fourth main winding. This circuit is
not illustrated in the figure, since the figure is only intended to illustrate the
relative positions of the windings.
[0050] In the topologies which are considered to be preferred in the present description,
however, it is the case that the turns in the main winding follow the field direction
from the control field and the turns in the control winding follow the field direction
to the main field.
[0051] Figures 1b-1g illustrate the definition of the axes and the direction of the different
windings and the magnetic body. With regard to the windings, we shall call the axis
the perpendicular to the surface which is restricted by each turn. The main winding
2 will have an axis A2, the main winding 3 an axis A3 and the control winding 4 an
axis A4.
[0052] With regard to the magnetisable body, the longitudinal direction will vary with respect
to the shape. If the body is elongated, the longitudinal direction A1 will correspond
to the body's longitudinal axis. If the magnetic body is square as illustrated in
figure 1a, a longitudinal direction A1 can be defined for each leg of the square.
Where the body is tubular, the longitudinal direction A1 will be the tube's axis,
and for an annular body the longitudinal direction A1 will follow the ring's circumference.
[0053] The device is based on the possibility of altering the characteristics of the magnetisable
body 1 in relation to a first magnetic field by altering a second magnetic field which
is at right angles to the first. Thus, for example, the field H1 can be defined as
the working field and control the body's 1 characteristics (and thereby the behaviour
of the working field H1) by means of the field H2 (hereinafter called control field
H2). This will now be explained in more detail.
[0054] The magnetisation current in an electrical conductor which is enclosed by a ferromagnetic
material is limited by the reluctance according to Faraday's Law. The flux which has
to be established in order to generate counterinduced voltage depends on the reluctance
in the magnetic material enclosing the conductor.
[0055] The extent of the magnetisation current is determined by the amount of flux which
has to be established in order to balance applied voltage. In general the following
steady-state equation applies for sinusoidal voltage:
1) Flux:
E = applied voltage
ω = angular frequency
N = number of turns for winding
where the flux Φ through the magnetic material is determined by the voltage E. The
current required in order to establish necessary flux is determined by:
2) Current
3) Reluctance (flux resistance)
lj = length of flux path
µr = relative permeability
µo = permeability in vacuum
Aj = cross-sectional area of the flux path
[0056] Where there is low reluctance (iron enclosure), according to expression 2) above,
little current will be required in order to establish the necessary flux, and supplied
voltage will overlay the connector. In the case of high reluctance (air) on the other
hand, a large current will be required in order to establish the necessary flux. In
this case the current will then be limited by the voltage over the load and the voltage
induced in the connector. The difference between reluctance in air and reluctance
in magnetic material may be of the order of 1.000 - 900.000.
[0057] The magnetic induction or flux density in a magnetic material is determined by the
material's relative permeability and the magnetic field intensity. The magnetic field
intensity is generated by the current in a winding arranged round or through the material.
[0058] For the systems which have to be evaluated the following applies:
The field intensity
= field intensity
s = the integration path
I = current in winding
N = number of windings
Flux density or induction:
= magnetic field intensity
[0059] The ratio between magnetic induction and field intensity is non-linear, with the
result that when the field intensity increases above a certain limit, the flux density
will not increase and on account of a saturation phenomenon which is due to the fact
that the magnetic domains in a ferromagnetic material are in a state of saturation.
Thus it is desirable to provide a control field H2 which is perpendicular to a working
field H1 in the magnetic material in order to control the saturation in the magnetisable
material, while avoiding magnetic connection between the two fields and thereby avoiding
transformative or inductive connection. Transformative connection means a connection
where two windings "share" a field, with the result that a change in the field from
one winding will lead to a change in the field in the other winding.
[0060] One will avoid increasing H to saturation as by a transformative connection where
the fluxes will have a common path and will be added together. If the fluxes are orthogonal
they will not be added together. For example, by providing the magnetic material as
a tube where the main winding or the winding which carries the working current is
located inside the tube and is wound in the tube's longitudinal direction, and where
the control winding or the winding which carries the control current is wound round
the circumference of the tube, the desired effect is achieved. Depending on the tube
dimensions, a small area for the control flux and a large area for the working flux
are thereby also achieved.
[0061] In the said embodiment not according to the invention, the working flux will travel
in the direction along the tube's circumference and have a closed magnetic circuit.
The control flux on the other hand will travel in the tube's longitudinal direction
and will have to be connected in a closed magnetic circuit, either by two tubes being
placed in parallel and a magnetic material connecting the control flux between the
two tubes, or by a first tube being placed around a second tube, with the result that
the control winding is located between the two tubes, and the end surfaces of the
tubes are magnetically interconnected, thereby obtaining a closed path for the control
flux. These solutions will be described in greater detail later.
[0062] The parts which provide magnetic connection between the tubes or the core parts will
hereinafter be called magnetic field connectors or magnetic field couplings.
[0063] The total flux in the material is given by
[0064] The flux density B is composed of the vector sum of B1 and B2 (fig. 4d). B1 is generated
by the current 11 in the first main winding 2, and B1 has a direction tangentially
to the conductors in the main winding 2. The main winding 2 has N1 turns and is wound
round the magnetisable body 1. B2 is generated by the current 12 in the control winding
4 with N2 number of turns and where the control winding 4 is wound round the body
1. B2 will have a direction tangentially to the conductors in the control winding
4.
[0065] Since the windings 2 and 4 are placed at 90° to each other, B1 and B2 will be orthogonally
located. In the magnetisable body 1, B1 will be oriented transversally and B2 longitudinally.
In this connection we refer particularly to what is illustrated in figs. 1-4.
[0066] It is considered an advantage that the relative permeability is higher in the working
field's (H1) direction than in the control field's (H2) direction, i.e. the magnetic
material in the magnetisable body 1 is anisotropic.
[0067] The vector sum of the fields H1 and H2 will determine the total field in the body
1, and thus the body's 1 condition with regard to saturation, and will be determining
for the magnetisation current and the voltage which is divided between a load connected
to the main winding 2 and the connector. Since the sources for B1 and B2 will be located
orthogonally to each other, none of the fields will be able to be decomposed into
the other. This means that B1 cannot be a function of B2 and vice versa. However,
B, which is the vector sum of B1 and B2 will be influenced by the extent of each of
them.
[0068] B2 is the vector which is generated by the control current. The cross-sectional surface
A2 for the B2 vector will be the transversal surface of the magnetic body 1, cf. figure
4c. This may be a small surface limited by the thickness of the magnetisable body
1, given by the surface sector between the internal and external diameters of the
body 1, in the case of an annular body. The cross-sectional surface A1 (see figures
4a, b) for the B1 field on the other hand is given by the length of the magnetic core
and the rating of applied voltage. This surface will be able to be 5-10 times larger
than the surface of the control flux density B2, without this being considered limiting
for the invention.
[0069] When B2 is at saturation level, a change in B1 will not result in a change in B.
This makes it possible to control which level on B1 gives saturation of the material,
and thereby control the reluctance for B.
[0070] The inductance for the control winding 4 (with N2 turns) will be able to be rated
at a small value suitable for pulsed control of the regulator, i.e. enabling a rapid
reaction (of the order of milliseconds) to be provided.
N2 = Number of turns for control winding
A2 = Area of control flux density B2
l2 = Length of flux path for control flux
[0071] A simplified mathematical description will now be given based on Maxwell's equations.
[0072] For simple calculations of magnetic fields in electrical power technology, Maxwell's
equations are used in integral form.
[0073] In a device of the type which will be analysed here the magnetic field has low frequency.
[0074] The displacement current can thus be neglected compared with the current density.
Maxwell's equation
is simplified to
[0075] The integral form is found in Toke's theorem:
presents a solution for the system in fig. 4, where the main winding 2 establishes
the H1 field. The calculations are performed here with concentrated windings in order
to be able to focus on the principle and not an exact calculation.
[0076] The integration path coincides with the field direction and an average field length
11 is chosen in the magnetisable body 1. The solution of the integral equation then
becomes:
[0077] This is also known as the magnetomotive force MMK.
[0078] The control winding 4 will establish a corresponding MMK generated by the current
I2:
[0079] The magnetisation of the material under the influence of the H field which is generated
from the source windings 2 and 4 is expressed by the flux density B. For the main
winding 2:
[0080] For the control winding 4:
[0081] The permeability in the transversal direction is of the order of 1 to 2 decades less
than for the longitudinal direction. The permeability for vacuum is:
[0082] The capacity to conduct magnetic fields in iron is given by µ
r, and the magnitude of µ is from 1000 to 100.000 for iron and for the new Metglas
materials up to 900.000.
[0083] By combining equations 11) and 15), for the main winding 2 we get:
[0084] The flux in the magnetisable body 1 from the main winding 2 is given by equation:
[0085] Assuming the flux is constant over the core cross section:
[0086] Here we recognise the expression for the flux resistance Rm or the reluctance as
given under 3):
[0087] In the same way we find flux and reluctance for the control winding 4:
[0088] The operation of the device is based on the physical fact that the differential of
the magnetic field intensity which has its source in the current in a conductor is
expressed by curl to the H field. Curl to H says something about the differential
or the field change of the H field across the field direction of H. In our case we
have calculated the field on the basis that the surface perpendicular of the differential
field loop has the same direction as the current. This means that the fields from
the current-carrying conductors forming the windings which are perpendicular to each
other are also orthogonal. The fact that the fields are perpendicular to each other
is important in relation to the orientation of the domains in the material.
[0089] Before examining this more closely, let us introduce self-inductance which will play
a major role in the application of the new magnetically controlled power components.
[0090] According to Maxwell's equations, a time-varying magnetic field will induce a time-varying
electrical field, expressed by
[0091] The left side of the integral is an expression of the potential equation in integral
form. The source of the field variation may be the voltage from a generator and we
can express Faraday's Law when the winding has N turns and all flux passes through
all the turns, see fig. 5:
[0092] λ (Wb) gives an expression of the number of flux turns and is the sum of the flux
through each turn in the winding. If one envisages the generator G in fig. 5 being
disconnected after the field is established, the source of the field variation will
be the current in the circuit and from circuit technology we have, see fig. 5a:
[0093] From equation 21 we have:
[0094] When L is constant, the combination of equations 26 and 27 gives:
[0095] The solution of 29 is:
[0096] From 28 we derive that C is 0 and:
[0097] This is an expression of self-inductance for the winding N (or in our case the main
winding 2). The self-inductance is equal to the ratio between the flux turns established
by the current in the winding (the coil) and the current in the winding (the coil).
[0098] The self-inductance in the winding is approximately linear as long as the magnetisable
body or the core are not in saturation. However, we shall change the self-inductance
through changes in the permeability in the material of the magnetisable body by changing
the domain magnetisation in the transversal direction by the control field (i.e. by
the field H2 which is established by the control winding 4).
[0099] From equation 21) combined with 31) we obtain:
[0100] The alternating current resistance or the reactance in an electrical circuit with
self-inductance is given by
[0101] By magnetising the domains in the magnetisable body in the transversal direction,
the reluctance of the longitudinal direction will be changed. We shall not go into
details here in the description of what happens to the domains during different field
influences. Here we have considered ordinary commercial electroplate with a silicon
content of approximately 3%, and in this description we shall not offer an explanation
of the phenomenon in relation to the Metglas materials, but the magnetic materials
with amorphous structure will be able to play an important role in some applications.
[0102] In a transformer we employ closed cores with high permeability where energy is stored
in magnetic leakage fields and a small amount in the core, but the stored energy does
not form a direct part in the transformation of energy, with the result that no energy
conversion takes place in the sense of what occurs in an electromechanical system
where electrical energy is converted to mechanical energy, but energy is transformed
via magnetic flux through the transformer. In an inductance coil or choke with an
air gap, the reluctance in the air gap is dominant compared to the reluctance in the
core, with approximately all the energy being stored in the air gap.
[0103] In the device, a "virtual" air gap is generated through saturation phenomena in the
domains. In this case the energy storage will take place in a distributed air gap
comprising the whole core. We consider the actual magnetic energy storage system to
be free for losses, and any losses will thus be represented by external components.
[0104] The energy description which we use will be based on the principle of conservation
of energy.
[0105] The first law of thermodynamics applied to the loss-free electromagnetic system above
gives, see fig. 6:
where
dWelin = differential electrical energy supply
dWfld = differential change in magnetically stored energy
[0106] From equation 26) we have
[0107] Now our inductance is variable through the orthogonal field or the control field
H2, and equation 31) inserted in 26) gives:
[0108] The effect within the system is
[0109] Thus we have
[0110] For a system with a core where the reluctance can be varied and which only has a
main winding, equation 35) inserted in equation 37) will give
[0111] In the device, L will be varied as a function of µr, the relative permeability in
the magnetisable body or the core 1, which in turn is a function of I2, the control
current in the control winding 4.
[0112] When L is constant, i.e. when 12 is constant, we can disregard the section i x dL
since dL is equal to 0, and thus the magnetic field energy will be given by:
[0113] When L is varied by means of I2, the field energy will be altered as a result of
the altered value of L, and thereby the current I will also be altered since it is
associated with the field value through the flux turns λ. Since i and λ are variable
and functions of each other, while being non-linear functions, we shall not go into
the solution here since it will involve mathematics which exceed the bounds of the
description necessary to understand the device.
[0114] However, we can draw the conclusion that the field energy and the energy distribution
will be controllable via µr and influence how energy stored in the field is increased
and decreased. When the field energy is decreased, the surplus portion will be returned
to the generator. Or if we have an extra winding (e.g. winding 3, figure 1) in the
same winding window as the first main winding 2 and with the same winding axis as
it has, this will provide a transformative transfer of energy from the first winding
2 to the second main winding 3.
[0115] This is illustrated in fig. 7 where an alteration of λ results in an alteration of
the energy in the field Wflt which originally is Wflt(λo, io). A variation is envisaged
here which is so small that i is approximately constant during the alteration of λ.
In the same way an alteration of i will give an alteration of λ. When we look at our
variable inductance, therefore, we can say the following:
[0116] The substance of what takes place is illustrated in fig. 8 and fig. 9.
[0117] Fig. 8 illustrates the magnetisation curves for the entire material of the magnetisable
body 1 and the domain change under the influence of the H1 field from the main winding
2.
[0118] Fig. 9 illustrates the magnetisation curves for the entire material of the magnetisable
body 1 and the domain change under the influence of the H2 field in the direction
from the control winding 4.
[0119] Figs. 10a and 10b illustrate the flux densities B1 (where the field H1 is established
by the working current), and B2 (corresponding to the control current). The ellipse
illustrates the saturation limit for the B fields, i.e. when the B field reaches the
limit, this will cause the material of the magnetisable body 1 to reach saturation.
The form of the ellipse's axes will be given by the field length and the permeability
of the two fields B1 (H1) and B2 (H2) in the core material of the magnetisable body
1.
[0120] By having the axes in figure 10 express the MMK distribution or the H field distribution,
a picture can be seen of the magnetomotive force from the two currents I1 and I2.
[0121] We now refer back to figures 8 and 9. By means of a partial magnetisation of the
domains by the control field B2 (H2), an additional field B1 (H1) from the main winding
2 will be added vectorially to the control field B2 (H2), further magnetising the
domains, with the result that the inductance of the main winding 2 will start from
the basis given by the state of the domains under the influence of the control field
B2 (H2).
[0122] The domain magnetisation, the inductance L and the alternating current resistance
XL will thereby be varied linearly as a function of the control field B2.
[0123] We shall now describe the several variants of the device, with reference to the remaining
figures.
[0124] Figure 11 is a schematic illustration of a second embodiment not according to the
invention.
[0125] Figure 12 illustrates the same embodiment of a magnetically influenced connector
not according to the invention, where Fig. 12a illustrates the assembled connector
and Fig. 12b illustrates the connector viewed from the end.
[0126] Figure 13 illustrates a section along line II in figure 12b.
[0127] As illustrated in the figures the magnetisable body 1 is composed of inter alia two
parallel tubes 6 and 7 made of magnetisable material. An electrically insulated conductor
8 (figs. 12a, 13) is passed continuously in a path through the first tube 6 and the
second tube 7 N number of times, where N = 1, ... r, forming the first main winding
2, with the conductor 8 extending in the opposite direction through the two tubes
6 and 7, as is clearly illustrated in fig. 13. Even though the conductor 8 is only
shown extending through the first tube 6 and the second tube 7 twice, it should be
self-explanatory that it is possible for the conductor 8 to extend through respective
tubes either only once or possibly several times (as indicated by the fact that the
winding number N can vary from 0 to r), thus creating a magnetic field H1 in the parallel
tubes 6 and 7 when the conductor is excited. A combined control and magnetisation
winding 4, 4', composed of the conductor 9, is wound round the first tube and the
second tube (6 and 7 respectively) in such a manner that the direction of the field
H2 (B2) which is created in the said tubes when the winding 4 is excited will be oppositely
directed, as indicated by the arrows for the field B2 (H2) in figure 11. The magnetic
field connectors 10, 11 are mounted at the ends of the respective pipes 6, 7 in order
to interconnect the tubes fieldwise in a loop. The conductor 8 will be able to carry
a load current 11 (fig. 12a). The tubes' 6, 7 length and diameter will be determined
on the basis of the power and voltage which have to be connected. The number of turns
N1 on the main winding 2 will be determined by the reverse blocking ability for voltage
and the cross-sectional area of the extent of the working flux φ2. The number of turns
N2 on the control winding 4 is determined by the fields required for saturation of
the magnetisable body 1, which comprises the tubes 6, 7 and the magnetic field connectors
10, 11.
[0128] Figure 14 illustrates a special design of the main winding 2 in a device not according
to the invention. In reality, the solution in fig. 14 differs from that illustrated
in figs. 12 and 13 only by the fact that instead of a single insulated conductor 8
which is passed through the pipes 6 and 7, two separate oppositely directed conductors,
so-called primary conductors 8 and secondary conductors 8' are employed, in order
thereby to achieve a voltage converter function for the magnetically influenced device
not according to the invention. This will now be explained in more detail. The design
is basically similar to that illustrated in figs. 11, 12 and 13. The magnetisable
body 1 comprises two parallel tubes 6 and 7. An electrically insulated primary conductor
8 is passed continuously in a path through the first tube 6 and the second tube 7
N1 number of times, where N1 = 1, ... r, with the primary conductor 8 extending in
the opposite direction through the two tubes 6 and 7. An electrically insulated secondary
conductor 8' is passed continuously in a path through the first tube 6 and the second
tube 7 N1' number of times, where N1' = 1, ... r, with the secondary conductor 8'
extending in the opposite direction relative to the primary conductor 8 through the
two tubes 6 and 7. At least one combined control and magnetisation winding 4 and 4'
is wound round the first tube 6 and the second tube 7 respectively, with the result
that the field direction created on the said tube is oppositely directed. As for the
embodiment not according to the invention, and illustrated in Figs. 11, 12 and 13,
magnetic field connectors 10, 11 are mounted on the end of respective tubes (6, 7)
in order to interconnect the tubes 6 and 7 fieldwise in a loop, thereby forming the
magnetisable body 1. Even though for the sake of simplicity the primary conductor
8 and the secondary conductor 8' are illustrated in the drawings with only one pass
through the tubes 6 and 7, it will be immediately apparent that both the primary conductor
8 and the secondary conductor 8' will be able to be passed through the tubes 6 and
7 N1 and N1' number of times respectively. The tubes' 6 and 7 length and diameter
will be determined on the basis of the power and voltage which have to be converted.
For a transformer with a conversion ratio (N1:N1') equal to 10:1, in practice ten
conductors will be used as primary conductors 8 and only one secondary conductor 8'.
[0129] An embodiment, that is not according to the invention, of magnetic field connectors
10 and/or 11 is illustrated in figure 15. A magnetic field connector 10, 11 is illustrated,
composed of a magnetically conducting material, wherein two preferably circular apertures
12 for the conductor 8 in the main winding 2 (see, e.g. fig. 13) are machined out
of the magnetic material in the connectors 10, 11. Moreover, there is provided a gap
13 which interrupts the magnetic field path of the conductor 8. End surface 14 is
the connecting surface for the magnetic field H2 from the control winding 4 consisting
of conductors 9 and 9' (fig. 13).
[0130] Fig. 16 illustrates a thin insulating film 15 which will be placed between the end
surface on tubes 6 and 7 and the magnetic field connector 10, 11 in a preferred variant
of the above-described device that is not according to the invention.
[0131] Figures 17 and 18 illustrate other alternative variants of the above-described device
that is not according to the invention, in connection with the magnetic field connectors
10, 11. Figures 19-32 illustrate several variants of the above-described device that
is not according to the invention, in connection with a core 16 which, in the variants
illustrated in Figures 12, 13 and 14, forms the main part of the tubes 6 and 7 which
preferably together with the magnetic field connectors 10 and 11 form the magnetisable
body 1.
[0132] Fig. 19 illustrates a cylindrical core part 16 which is divided lengthwise as illustrated
and where there are placed one or more layers 17 of an insulating material between
the two core halves 16', 16".
[0133] Fig. 20 illustrates a rectangular core part 16 and Fig. 21 illustrates a variant
of this core part 16 where it is divided in two with partial sections in the lateral
surface. In the variant illustrated in Fig. 21, one or more layers of an insulating
material 17 are provided between the core halves 16, 16'. A further variant is illustrated
in figure 22 where the partial section is placed in each corner.
[0134] Figs. 23, 24 and 25 illustrate a rectangular shape. Figures 26, 27 and 28 illustrate
the same for a triangular shape. Figs. 29 and 30 illustrate an oval variant, and fmally
figures 31 and 32 illustrate a hexagonal shape. In figure 31, the hexagonal shape
is composed of 6 equal surfaces 18 and in Fig. 30 the hexagon consists of two parts
16' and 16". Reference numeral 17 refers to a thin insulating film.
[0135] Figures 33 and 34 illustrate a magnetic field connector 10, 11 which can be used
as a control field connector between the rectangular and square main cores 16 (illustrated
in figures 20-21 and 23-25 respectively). This magnetic field connector comprises
three parts 10', 10" and 19.
[0136] Fig. 34 illustrates a variant of the core part or main core 16 where the end surface
14 or the connecting surface for the control flux is at right angles to the axis of
the core part 16.
[0137] Fig. 35 illustrates a second variant of the core part 16 where the connecting surface
14 for the control flux is at an angle α to the axis of the core part 16.
[0138] Figures 36-38 illustrate various designs of the magnetic field connector 10, 11,
which are based on the fact that the connecting surfaces 14' of the magnetic field
connector 10, 11 are at the same angle as the end surfaces 14 to the core part 16.
[0139] Fig. 36 illustrates a magnetic field connector 10, 11 not according to the invention,
in which different hole shapes 12 are indicated for the main winding 2 on the basis
of the shape of the core part 16 (round, triangular, etc.).
[0140] In Fig. 37, the magnetic connector 10, 11 is flat. It is adapted for use with core
parts 16 with right-angled end surfaces 14.
[0141] In Fig. 38, an angle α' is indicated to the magnetic field connector 10, 11, which
is adapted to the angle α to the core part (figure 35), thus causing the end surface
14 and the connecting surface 14' to coincide.
[0142] In Fig. 39, a variant of the above-discussed device that is not according to the
invention is illustrated with an assembly of magnetic field connectors 10, 11 and
core parts 16. Figure 39b illustrates the same variant viewed from the side.
[0143] It is possible to switch the positions of the control winding and the main winding.
[0144] Figures 40 and 41 are a sectional illustration and view respectively of the first-mentioned
embodiment of the invention, of a magnetically influenced voltage connector device.
The device comprises (see figure 40b) a magnetisable body 1 comprising an external
tube 20 and an internal tube 21 (or core parts 16, 16') which are concentric and made
of a magnetisable material with a gap 22 between the external tube's 20 inner wall
and the internal tube's 21 outer wall. Magnetic field connectors 10, 11 between the
tubes 20 and 21 are mounted at respective ends thereof (fig. 40a). A spacer 23 (fig.
40a) is placed in the gap 22, thus keeping the tubes 20, 21 concentric. A combined
control and magnetisation winding 4 composed of conductors 9 is wound round the internal
tube 21 and is located in the said gap 22. The winding axis A2 for the control winding
therefore coincides with the axis A1 of the tubes 20 and 21. An electrical current-carrying
or main winding 2 composed of the current conductor 8 is passed through the internal
tube 21 and along the outside of the external tube 20 N1 number of times, where N1
= 1, ... r. With the combined control and magnetisation winding 4 in co-operation
with the main winding 2 or the said current-carrying conductor 8, an easily constructed
but efficient magnetically influenced voltage connector is obtained. This embodiment
of the device may also be modified in such a manner that the tubes 20, 21 do not have
a circular cross section, but a cross section which is square, rectangular, triangular,
etc.
[0145] It is also possible to wind the main winding round the internal tube 21, in which
case the axis A2 of the main winding will coincide with the axis A1 of the tubes,
while the control winding is wound about the tubes on the inside of 21 and the outside
of 20.
[0146] Figs. 42-44 illustrate various configurations of the magnetic field connector 10,
11 which are specially adapted to the latter design of the device, i.e. as described
in connection with Figures 40 and 41.
[0147] Figure 42a illustrates in section and figure 42b in a view from above a magnetic
field connector 10, 11 with connecting surfaces 14' at an angle relative to the axis
of the tubes 20, 21 (the core parts 16) and it is obvious that the internal 21 and
external 20 tubes should also be at the same angle to the connecting surfaces 14.
[0148] Figs. 43 and 44 illustrate other variants of the magnetic field , connector 10, 11,
where the connecting surfaces 14' of the control field H2 (B2) are perpendicular to
the main axis of the core parts 16 (tubes 20, 21).
[0149] Figure 43 illustrates a hollow semi-toroidal magnetic field connector 10, 11 with
a hollow semi-circular cross section, while figure 44 illustrates a toroidal magnetic
field connector with a rectangular cross section.
[0150] A variant of the device illustrated in Figures 40 and 41 is illustrated in Fig. 45,
where Figure 45a illustrates the device from the side while 45b illustrates it from
above. The only difference from the voltage connector in figs. 40-41 is that a second
main winding 3 is wound in the same course as the main winding 2. By this means an
easily constructed, but efficient magnetically influenced voltage converter is obtained.
[0151] Figures 46 and 47 are a section and a view illustrating the other embodiment of the
voltage connector with concentric tubes.
[0152] Figures 46 and 47 illustrate the voltage connector which acts as a voltage converter
with joined cores. An internal reluctance-controlled core 24 is located within an
external core 25 round which is wound a main winding 2. The reluctance-controlled
internal core 24 has the same construction as mentioned previously under the description
of figs. 40 and 41, but the only difference is that there is no main winding 2 round
the core 24. It has only a control winding 4 which is located in the gap 22 between
the inner 21 and outer parts forming the internal reluctance-controlled core 24, with
the result that only core 24 is magnetically reluctance-controlled under the influence
of a control field H2 (B2) from current in the control winding 4.
[0153] The main winding 2 in figs. 46 and 47 is a winding which encloses both core 24 and
core 25.
[0154] The mode of operation of the reluctance-controlled voltage connector or converter
according to the invention and described in connection with figures 46 and 47 will
now be described.
[0155] We shall also refer to Figure 55 which illustrates a device not according to the
invention, but which illustrates the principle of the connection, figure 65 with a
simplified equivalent diagram for the reluctance model where Rmk is the variable reluctance
which controls the flux between the windings 2 and 3, and figure 65b which illustrates
an equivalent electrical circuit for the connection where Lk is the variable inductance.
[0156] An alternating voltage V1 over winding 2 will establish a magnetisation current I1
in winding 2. This is generated by the flux φ1 + φ1' in the cores 24 and 25 which
requires to be established in order to provide the bucking voltage which according
to Faraday's Law is generated in 2. When there is no control current in the reluctance-controlled
core 24, the flux will be divided between the cores 24 and 25 based on the reluctance
in the respective cores 24 and 25.
[0157] In order to bring energy through from one winding to the other, the internal reluctance-controlled
core 24 has to be supplied with control current 12.
[0158] By supplying control current 12 in the positive half-period of the alternating voltage
V1 in 2, we shall obtain a half-period voltage over 2. Since the energy is transferred
by flux displacement between the reluctance-controlled core 24 and the external (secondary)
core 25, the reluctance-controlled core 24 will essentially be influenced by the control
current 12 during the period when it is controlled in saturation, while the working
flux will travel in the secondary external core 25 and interact with the primary winding
2 during the energy transfer.
[0159] When the reluctance-controlled core 24 is brought out of saturation by resetting
the control flux B2 (H2) which is orthogonal to the working flux B1 (H1), the flux
from the primary side will again be divided between the cores 24 and 25, and a load
connected to the secondary winding 3 will only see a low reluctance and thereby high
inductance and little connection between primary (VI) and secondary (V3) voltage.
A voltage will be generated over the secondary winding 3, but on account of the magnitude
of Lk compared to the magnetisation impedance Lm, most of the voltage (V1) from the
primary winding 2 will overlay Lk. The flux from the primary winding 2 will essentially
go where there is the least reluctance and where the flux path is shortest (fig. 65b).
[0160] It may also be envisaged that the external core 25 could be made controllable, in
addition to having a fourth main winding wound round the internal controllable core
24. This is to enable the voltage between the cores 24 and 25 to be controlled as
required.
[0161] Fig. 48 describes a further device that is not according to the invention, of a magnetically
influenced voltage connector or voltage converter, where the magnetisable body 1 is
so designed that the control flux B2 (H2) is connected directly without a separate
magnetic field connector through the main core 16.
[0162] Fig. 48 illustrates a voltage connector, that is not according to the invention,
in the form of a toroid viewed from the side. The voltage connector comprises two
core parts 16 and 16', a main winding 2 and a control winding 4.
[0163] Fig. 49 illustrates a voltage connector, that is not according to the invention,
equipped with an extra main winding 3 which offers the possibility of converting the
voltage.
[0164] Fig. 50 illustrates the device in figure 48 in section along line VI-VI in figure
48 and figure 51 illustrates a section along line V-V. In figure 50 a circular aperture
12 is illustrated for placing the control winding 4.
[0165] Figure 51 illustrates an additional aperture 26 for passing through wiring.
[0166] Figures 52 and 53 illustrate the structure of a core 16, that is not according to
the invention, without windings and where the core 16 is so designed that there is
no need for an extra magnetic field connector for the control field. The core 16 has
two core parts 16, 16' and an aperture 12 for a control winding 4. This design is
intended for use where the magnetic material is sintered or compressed powder-moulded
material. In this case it will be possible to insert closed magnetic field paths in
the topology, with the result that what were previously separate connectors which
were required for foil-wound cores form part of the actual core and are a productive
part of the structure. The core, which forms the closed magnetic circuit without separate
magnetic field connectors and which is illustrated in these figures 52 and 53, will
be able to be used in all the devices that are not according to the invention even
though the figures illustrate a body 1 adapted for the device illustrated, inter alia,
in Figures 1 and 2.
[0167] Figure 54 illustrates a magnetically influenced voltage converter device according
to the invention, where the device has an internal control core 24 consisting of an
external tube 20 and an internal tube 21 which are concentric and made of a magnetisable
material with a gap 22 between the external tube's 20 inner wall and the internal
tube's 21 outer wall. Spacers 23 are mounted in the gap between the external tube's
20 inner wall and the internal tube's 21 outer wall. Magnetic field connectors 10,
11 are mounted between the tubes 20 and 21 at respective ends thereof. A combined
control and magnetisation winding 4 is wound round the internal tube 21 and is located
in the said gap 22. The device further consists of an external secondary core 25 with
windings comprising a plurality of ring core coils 25', 25", 25"' etc. placed on the
outside of the control core 24. Each ring core coil 25', 25", 25"' etc. consists of
a ring of a magnetisable material wound round by a respective second main winding
or secondary winding 3, only one of which is illustrated for the sake of clarity.
A first main winding or primary winding 2 is passed through the internal tube 21 in
the control core 24 and along the outside of the external cores 25 N1 number of times,
where N1 = 1, ... r.
[0168] It is also possible to envisage the secondary core device being located within the
control core 24, in which case the primary winding 2 will have to be passed through
the ring cores 25 and along the outside of the control core 24.
[0169] Figure 55 is a schematic illustration of a magnetically influenced voltage regulator,
not according to the invention, with a first reluctance-controlled core 24 and a second
core 25, each of which is composed of a magnetisable material and designed in the
form of a closed, magnetic circuit, the said cores being juxtaposed. At least one
first electrical conductor 8 is wound on to a main winding 2 about both the first
and the second core's cross-sectional profile along at least a part of the said closed
circuit. At least one second electrical conductor 9 is mounted as a winding 4 in the
reluctance-controlled core 24 in a form which essentially corresponds to the closed
circuit. In addition, at least one third electrical conductor 27 is wound round the
second core's 25 cross-sectional profile along at least a part of the closed circuit.
The field direction from the first conductor's 8 winding 2 and the second conductor's
9 winding is orthogonal. By means of this solution, the first conductor 8 and the
third conductor 27 form a primary winding 2 and a secondary winding 3 respectively.
[0170] Figure 56 illustrates a proposal for an electro-technical schematic symbol for the
voltage connector that is not according to the invention.
[0171] Fig. 57 illustrates a proposal for a block schematic symbol for the voltage connector.
[0172] Figure 58 illustrates a magnetic circuit, not according to the invention, where the
control winding 4 and control flux B2 (112) are not included.
[0173] In Figs. 59 and 60 there is a proposal for an electro-technical schematic symbol
for the voltage converter that is not according to the invention, where the reluctance
in the control core 24 shifts magnetic flux between a core with fixed reluctance 25
and a second core with variable reluctance 24 (see for example Figure 55).
[0174] There is, of course, no restriction to having two cores with variable reluctance.
The fact that we can shift flux between two cores within the same winding will be
employed in order to make a magnetic switch which can switch a voltage off and on
independently of the course of magnetisation in the main core. This means that we
have a switch which has the same function as a GTO, except that we can choose whatever
switching time we wish.
[0175] Devices that are according to the invention, and those described herein that are
not according to the invention, will be able to be used in many different connections
and examples will now be given of applications in which they will be particularly
suitable.
[0176] Figure 61 illustrates the use of devices disclosed herein according to, and not according
to, the invention in an alternating current circuit in order to control the voltage
over a load RL, which may be a light source, a heat source or other load.
[0177] Figure 62 illustrates the use of devices disclosed herein according to, and not according
to, the invention in a three-phase system where such a voltage connector in each phase,
connected to a diode bridge, is used for a linear regulation of the output voltage
from the diode bridge.
[0178] Figure 63 illustrates a use of devices disclosed herein according to, and not according
to, the invention as a variable choke in DC-DC converters.
[0179] Figure 64 illustrates a use of devices disclosed herein according to, and not according
to, the invention as a variable choke in a filter together with condensers. Here we
have only illustrated a series and a parallel filter (64a and 64b respectively), but
it is implicit that the variable inductance can be used in a number of filter topologies.
[0180] A further application of devices disclosed herein, that are not according to the
invention, is that described inter alia in connection with figures 14 and
45, where proposals for schematic symbols were given in Figure 59. In this application,
the voltage connector has a function as a voltage converter where a secondary winding
is added. An application as a voltage regulator is also illustrated here, where the
magnetisation current in the transformer connection and the leakage reactance are
controllable via the control winding 4. The special feature of this system is that
the transformer equations will apply, while at the same time the magnetisation current
can be controlled by changing µr. In this case, therefore, the characteristic of the
transformer can be regulated to a certain extent. If there is a DC excitation of one
winding 2, it will be possible to obtain transformed energy through the transformer
by varying µr and thereby the flux in the reluctance-controlled core instead of varying
the excitation. Thus it is possible in principle to generate an AC voltage from a
DC voltage by means of the fact that an alteration of the magnetisation current from
the DC generator into this system will be able to be transformed to a winding on the
secondary side.
[0181] An application of the invention is illustrated in Figures 46 and 47, where a variable
reluctance as control core is surrounded or enclosed by one or more separate cores
with separate windings, as well as Figure 55 where a device that is not according
to the invention as illustrated with a first reluctance-controlled core and a second
core are designed as closed magnetic circuits and are juxtaposed. We also refer to
Figure 65 which illustrates an equivalent electrical circuit.
[0182] Figure 55 illustrates how the fluxes in a device that is not according to the invention
travel in the cores. We wish to emphasise that the flux in the control core is connected
to the flux in the working core via the windings enclosing both cores. In this system
transformation of electrical energy will be able to be controlled by flux being connected
to and disconnected from a control core and a working core. Since the fluxes between
the cores are interconnected through Faraday's induction law, the functional dependence
of the equations for the primary side and the equations for the secondary side will
be controlled by the connection between the fluxes. In a linear application we will
be able to control a transformation of voltages and currents between a primary winding
and a secondary winding linearly by altering the reluctance in the control core, thus
permitting us to introduce here the term reluctance-controlled transformer. For a
switched embodiment we will be able to introduce the term reluctance-controlled switch.
[0183] The flux connection between the primary or first main winding 2 and the secondary
winding or second main winding 3 will now be explained. Winding 2 which now encloses
both the reluctance-controlled control core 24 and the main core 25 will establish
flux in both cores. The self-inductance L1 to 2 tells how much flux, or how many flux
turns are produced in the cores when a current is passed in 11 in 2. The mutual inductance
between the primary winding 2 and the secondary winding 3 indicates how many of the
flux turns established by 2 and I1 are turned about 2 and about the secondary winding
3.
[0184] We may, of course, also envisage the main core 25 being reluctance-controlled, but
for the sake of simplicity we shall refer here to a system with a main core 25 where
the reluctance is constant, and a control core 24 where the reluctance is variable.
[0185] The flux lines will follow the path which gives the highest permeance (where the
permeability is highest), i.e. with the least reluctance.
[0186] In Figs. 55 and 65 we have not taken into consideration the leakage fields in the
main windings 2 and 3. Fig. 55 illustrates a simplified model of the transformer,
that is not according to the invention, where the primary 2 and secondary 3 windings
are each wound around a transformer leg, while in practice they will preferably be
wound on the same transformer leg, and in our case, for example, the outer ring core
which is the main core 25 will be wound around the secondary winding 3 distributed
along the entire core 25. Similarly, the primary winding 2 will be wound around the
main core 25 and the control core 24 which may be located concentrically and within
the main core.
[0187] Figure 65 illustrates a simplified reluctance model for the device according to the
invention.
[0188] Fig. 65b illustrates a simplified electrical equivalent diagram for the connector
according to the invention, where the reluctances are replaced by inductances.
[0189] A current in 2 generates flux in the cores 24 and 25:
where:
Φp = total flux established by the current in 2.
Φk = the total flux travelling through the control core 24.
Φl = part of the total flux travelling through the main core 25.
[0190] Since the leakage flux in main core 24 and control core 25 are disregarded,
[0191] In a way Φ
k may be regarded as a controlled leakage flux.
[0192] On the basis of fig. 65 we can formulate the highly simplified electrical equivalent
diagram for the magnetic circuit illustrated in fig. 65b.
[0193] Figure 65b therefore illustrates the principle of the reluctance-controlled connector,
where the inductance L
k absorbs the voltage from the primary side.
[0194] This inductance is controlled through the variable reluctance in the control core
24, with the result that the connection or the voltage division for a sinusoidal steady-state
voltage applied to the primary winding will be approximately equal to the ratio between
the inductance in the respective cores as illustrated in equation 43.
[0195] When the control core 24 is in saturation, L
k is very small compared to L
m and the voltage division will be according to the ratio between the number of turns
N1/N3. When the control core is in the off state, L
k will be large and to the same extent will block voltage transformation to the secondary
side.
[0196] The magnetisation of the cores relative to applied voltage and frequency is so rated
that the main core 25 and the control core 24 can each separately absorb the entire
time voltage integral without going into saturation. In our model the area of iron
on the control and working cores is equal without this being considered as limiting
for the invention.
[0197] Since the control core 24 is not in saturation on account of the main winding 2,
we shall be able to reset the control core 24 independently of the working flux B1
(H1), thereby achieving the object by means of the invention of realising a magnetic
switch. If necessary the main core 25 may be reset after an on pulse or a half on
period by the necessary MMF being returned in the second half-period only in order
to compensate for any distortions in the magnetisation current.
[0198] In a switched application, when the switch is off, i.e. when the flux on the primary
winding 2 is distributed between the control core 24 and the working core 25, the
flux connection between the primary 2 and the secondary 3 winding will be slight and
very little energy transfer takes place between primary 2 and secondary 3 winding.
[0199] When the switch is on, i.e. when the reluctance in the control core 24 is very low
(µr = 10-50) and approaching the reluctance of an air coil, we will have a very good
flux connection between primary 2 and secondary 3 winding and transfer of energy.
[0200] An important application of the invention will thus be as a frequency converter with
reluctance-controlled switches and a DC-AC or AC-DC converter by employing the reluctance-controlled
switch in traditional frequency converter connections and rectifier connections.
[0201] A frequency converter variant may be envisaged realised by adding bits of sinus voltages
from each phase in a three-phase system, each connected to a separate reluctance-controlled
core which in turn is connected to one or more adding cores which are magnetically
connected to the reluctance-controlled cores through a common winding through the
adding cores and the reluctance-controlled cores. Parts of sinus voltages can then
be connected from the reluctance-controlled cores into the adding core and a voltage
with a different frequency is generated.
[0202] A DC-AC converter may be realised by connecting a DC voltage to the main winding
enclosing the working core, where this time the working core is also wound round a
secondary winding where we can obtain a sinus voltage by changing the flux connection
between working core and control core sinusoidally.
[0203] Fig. 66 illustrates the connection for a magnetic switch. This may, of course, also
act as an adjustable transformer.
[0204] Figures 67 and 67a illustrate an example of a three-phase design. All the other three-phase
rectifier connectors are, of course, also feasible. By means of connection to a diode
bridge or individual diodes to the respective outlets in a 12-pulse connector, an
adjustable rectifier is obtained.
[0205] In the application as an adjustable transformer, it must be emphasised that the size
of the reluctance-controlled core is determined by the range of adjustment which is
required for the transformer, (0-100% or 80-110%) for the voltage.
[0206] Figure 67b illustrates the use of the device according to the invention as a connector
in a frequency converter for converting input frequency to randomly selected output
frequency and intended for operation of an asynchronous motor, for adding parts of
the phase voltage generated from a 6 or 12-pulse transformer to each motor phase (figure
67b).
[0207] Fig. 68 illustrates the device used as a switch in a UFC (unrestricted frequency
changer with forced commutation).
[0208] Fig. 69 illustrates a circuit comprising 6 devices 28-33 according to the invention.
The devices 28-33 are employed as frequency converters where the period of the voltages
generated is composed of parts of the fundamental frequency. This works by "letting
through" only the positive half-periods or parts of the half-periods of a sinus voltage
in order to make the positive new half-period in the new sinus voltage, and subsequently
the negative half-periods or parts of the negative half-periods in order thereby to
make the negative half-periods in the new sinus voltage. In this way a sinus voltage
is generated with a frequency from 10% to 100% of the fundamental frequency. This
converter also acts as a soft start since the voltage on the output is regulated via
the reluctance control of the connection between the primary and the secondary winding.
[0209] In fig. 69, if the first half-period is allowed through connector no. 28 (main winding
2), the current through the secondary winding (main winding 3) in the same connector
will commutate to the secondary winding (main winding 3) in connector no. 29, and
on from 29 to 28, etc.
[0210] Fig. 70 illustrates the use of the device according to the invention as a DC to AC
converter. Here the main winding 2 in the connector is excited by a DC voltage U1
which establishes a field H1 (B1) both in the control core 24 and in the main core
25 (these are not shown in the figure). The number of turns N1, N2, N3 and the area
of iron are designed in such a manner that none of the cores are in saturation in
steady state. In the event of a control signal (i.e. excitation of the control winding
4) into the control core 24, the flux B2 (H2) therein will be transferred to the main
core 25 and a change in the flux B1 (H1) in this core 25 will induce a voltage in
the secondary winding (main winding 3). By having a sinusoidal control current I2,
a sinusoidal voltage will be able to be generated on the secondary side (main winding
3), with the same frequency as the control voltage U1.
[0211] Figure 70b illustrates the use of the invention as a converter with a change of reluctance.
[0212] Figure 71 illustrates a use of the device according to the invention as an AC-DC
converter. The same control principle is used here as that explained above in the
description of a frequency converter in fig. 69. Figure 71b illustrates a diagram
of the time of the device's input and output voltage.
[0213] As mentioned previously, the voltage connector according to the invention is substantially
without movable parts for the absorption of electrical voltage between a generator
and a load. The function of the connector is to be able to control the voltage between
the generator and the load from 0-100% by means of a small control current. A second
function will be purely as a voltage switch. A further function could be forming and
transforming of a voltage curve.
[0214] The new technology according to the invention will be capable of being used for upgrading
existing diode rectifiers, where there is a need for regulation. In connection with
12-pulse or 24-pulse rectifier systems, it will be possible to balance voltages in
the system in a simple manner while having controllable rectification from 0-100%.
[0215] With regard to the magnetic materials involved in the invention, these will be chosen
on the basis of a cost/benefit function. The costs will be linked to several parameters
such as availability on the market, produceability for the various solutions selected,
and price. The benefit functions are based on which electro-technical function the
material requires to have, including material type and magnetic properties. Magnetic
properties considered to be important include hysteresis loss, saturation flux level,
permeability, magnetisation capacity in the two main directions of the material and
magnetostriction. The electrical units frequency, voltage and power to the energy
sources and users involved in the invention will be determining for the choice of
material. Suitable materials include the following:
a) Iron - silicon steel: produced as a strip of a thickness approximately 0.1mm-0.3mm
and width from 10mm to 1100mm and rolled up into coils. Perhaps the most preferred
for large cores on account of price and already developed production technology. For
use at low frequencies.
b) Iron - nickel alloys (permalloys) and/or iron - cobalt alloys (permendur) produced
as a strip rolled up into coils. These are alloys with special magnetic properties
with subgroups where very special properties have been cultivated.
c) Amorphous alloys, Metglas: produced as a strip of a thickness of approximately
20µm - 50µm, width from 4mm to 200mm and rolled up into coils. Very high permeability,
very low loss, can be made with almost 0 magnetostriction. Exists in a countless number
of variants, iron-based, cobalt-based, etc. Fantastic properties but high price.
d) Soft ferrites: Sintered in special forms developed for the converter industry.
Used at high frequencies due to small loss. Low flux density. Low loss. Restrictions
on physically realisable size.
e) Compressed powder cores: Compressed iron powder alloy in special shapes developed
for special applications. Low permeability, maximum approximately 400-600 to-day.
Low loss, but high flux density. Can be produced in very complicated shapes.
[0216] All sintered and press-moulded cores can implement the topologies which are relevant
in connection with the invention without the need for special magnetic field connectors,
since the actual shape is made in such a way that closed magnetic field paths are
obtained for the relevant fields.
[0217] If cores are made based on rolled sheet metal, they will have to be supplemented
by one or more magnetic field connectors.
1. Magnetisch beeinflusster Strom- oder Spannungsregulator, umfassend:
einen ersten röhrenförmigen Körper (20) und einen zweiten, inneren röhrenförmigen
Körper (21), die beide aus einem magnetisierbaren Material bestehen und einen Magnetkreis
bereitstellen, wobei die Körper (20, 21) relativ zueinander konzentrisch sind und
somit eine gemeinsame Achse (A1) haben,
zumindest einen ersten elektrischer Leiter (8), der um die röhrenförmigen Körper (20,
21) um zumindest eine Windung gewickelt ist, die eine erste Hauptwicklung (2) bildet,
und zumindest einen zweiten elektrischen Leiter (9), der in einem Spalt (22) zwischen
den Körpern (20, 21) vorgesehen ist und um die gemeinsame Achse (A1) des Körpers um
zumindest eine Windung, die eine zweite Hauptwicklung oder Steuerwicklung (4) bildet,
gewickelt ist, oder
zumindest einen elektrischen Leiter (8), der in einem Spalt (22) zwischen den Körpern
(20, 21) vorgesehen ist und um die gemeinsame Achse (A1) der Körper um zumindest eine
Windung, die eine erste Hauptwicklung (2) bildet, gewickelt ist und zumindest einen
zweiten elektrischen Leiter (9), der um die röhrenförmigen Körper (20, 21) um zumindest
eine Windung, die eine zweite Hauptwicklung oder Steuerwicklung (4) bildet, gewickelt
ist,
wobei die Wicklungsachse (A2) für die Windung oder Windungen in der Hauptwicklung
(2) in einem rechten Winkel zur Wicklungsachse (A4) für die Windung oder Windungen
in der Steuerwicklung (4) mit dem Ziel des Bereitstellens orthogonaler Magnetfelder
(H1, B1; H2, B2) in den Körpern steht und
dadurch das Verhalten des magnetisierbaren Materials relativ zum Feld (H1, B1) in der Hauptwicklung
(2) mittels des Feldes (H2, B2) in der Steuerwicklung (4) steuert,
gekennzeichnet dadurch, dass
die ersten und zweiten Körper aus einer gewickelten Folie magnetischen Materials hergestellt
sind, und dass der Regulator mittels der ersten und zweiten Körper, eines ersten Magnetfeldverbinders
(10) und eines zweiten Magnetfeldverbinders (11) einen geschlossenen Magnetkreis für
die orthogonalen Magnetfelder (H1, B1, H2, B2) bereitstellt, wobei die ersten und
zweiten Magnetfeldverbinder die jeweiligen Endoberflächen der ersten und zweiten Körper
magnetisch verbinden.
2. Regulator gemäß Anspruch 1, dadurch gekennzeichnet, dass die Magnetfeldverbinder (10, 11) alle einen Spalt (13) umfassen, um das Einführen
des ersten (8) oder des zweiten Leiters (9) zu erleichtern und den Magnetfeldpfad
oder das Magnetfeld H1 (B1) vom Leiter (8, 9) zu unterbrechen.
3. Regulator gemäß Anspruch 1 oder 2, dadurch gekennzeichnet, dass er einen dritten elektrischen Leiter (27) umfasst, der um eine Windung gewickelt
ist, die eine dritte Hauptwicklung (3) bildet, wo die Wicklungsachse (A3) für die
Windung oder die Windungen in der dritten Hauptwicklung (3) mit der Wicklungsachse
(A2) für die Windung oder die Windungen in der ersten Hauptwicklung (2) koinzidiert
oder zu ihr parallel ist, und somit einen Transformatoreffekt zwischen den ersten
und den dritten Hauptwicklungen bereitstellt, wenn zumindest eine von ihnen angeregt
wird.
4. Regulator gemäß Anspruch 1 oder Anspruch 2, dadurch gekennzeichnet, dass er einen dritten elektrischen Leiter (27) umfasst, der um zumindest eine Windung
gewickelt ist, die eine dritte Hauptwicklung (3) bildet,
wobei die Wicklungsachse (A3) für die Windung oder die Windungen in der dritten Hauptwicklung
(3) mit der Wicklungsachse (A4) für die Windung oder die Windungen in der Steuerwicklung
(4) koinzidieren oder zu ihr parallel ist, wodurch ein Transformatoreffekt zwischen
der dritten Hauptwicklung (3) und der Steuerwicklung (4) bereitgestellt wird, wenn
zumindest eine von ihnen angeregt wird.
5. Regulator gemäß einem der Ansprüche 1 bis 4, dadurch gekennzeichnet, dass er einen zusätzlichen röhrenförmigen Körper umfasst, der einen äußeren Kern (25)
bereitstellt, der auf der Außenseite des ersten, externen röhrenförmigen Körpers (20)
montiert ist, wo die Körper (20, 21, 25) konzentrisch zueinander sind und somit eine
gemeinsame Achse (A1) aufweisen.
6. Regulator gemäß Anspruch 5, dadurch gekennzeichnet, dass er einen dritten elektrischen Leiter (27) umfasst, der um den externen Kern (25)
um eine Windung gewickelt ist, welche eine dritte Hauptwicklung (3) bildet, wobei
die Wicklungsachse (A3) für die Windung oder die Windungen in der dritten Hauptwicklung
(3) mit der Wicklungsachse (A2) für die Windung oder Windungen in der ersten Hauptwicklung
(2) übereinstimmt oder parallel dazu ist, wodurch ein Transformatoreffekt zwischen
den ersten zwei und den dritten Hauptwicklungen (3) vorgesehen ist, wenn zumindest
eine von ihnen angeregt wird, oder wo die Wicklungsachse (A3) für die Windung oder
Windungen in der dritten Hauptwicklung (3) mit der Wicklungsachse (A4) für die Windung
oder die Windungen in der Steuerwicklung (4) koinzidiert oder parallel dazu ist, wodurch
ein Transformatoreffekt zwischen der dritten Hauptwicklung (3) und der Steuerwicklung
bereitgestellt wird, wenn zumindest eine von ihnen angeregt wird.
7. Regulator gemäß Anspruch 5 oder Anspruch 6, dadurch gekennzeichnet, dass der äußere Kern (25) aus mehreren ringförmigen Teilen (25', 25", etc.) besteht und
dass die erste (2) und/oder die dritte Hauptwicklung (3) individuelle Wicklungen um
jeden ringförmigen Teil bilden.
8. Regulator gemäß einem der Ansprüche 5 bis 7, dadurch gekennzeichnet, dass der externe Kern (25) aus verschiedenen ringförmigen Teilen (25', 25", etc.) besteht
und dass die Steuerwicklung (4) und/oder die dritte Hauptwicklung (3) individuelle
Wicklungen um jeden ringförmigen Teil bilden.
9. Verwendung eines Regulators gemäß einem der vorstehenden Ansprüche als eine Komponente
in einem Frequenzwandler zum Umwandeln von Eingangsfrequenz zu beliebig ausgewählter
Ausgangsfrequenz, vorzugsweise vorgesehen für den Betrieb eines asynchronen Motors
in einer Direktumrichterverbindung.
10. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 als ein Verbinder in
einem Frequenzwandler zum Umwandeln einer Eingangsfrequenz in eine beliebig ausgewählte
Ausgangsfrequenz und vorgesehen zum Betrieb eines asynchronen Motors zum Summieren
der Teile der aus einem 6 oder 12-Pulstransformator erzeugten Phasenspannung an jede
Motorphase.
11. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 als ein Gleichstrom-
oder Wechselstromwandler, der Gleichstromspannung/-Strom in eine Wechselstromspannung/-Strom
einer beliebig ausgewählten Ausgangsfrequenz umwandelt, wo die gespeicherte magnetische
Energie in einer Gleichstrom-betriebenen ersten Hauptwicklung oder Primärwicklungsinduktanz
mittels des orthogonalen Steuerfeldes variiert wird, welches die Induktion beeinflusst,
wodurch eine Wechselspannung in der dritten Hauptwicklung oder der sekundären Wicklung
im Spannungsverbinder mit einer Frequenz gleich der Frequenz der Fluxvariation/Induktionsvariation
erzeugt wird.
12. Verwendung eines Regulators gemäß Anspruch 11, wo drei solche variablen Induktionsspannungswandler
verbunden sind, um eine Dreiphasenspannung mit beliebig ausgewählter Ausgangsfrequenz
zu erzeugen, die mit der asynchronen Maschine verbunden ist.
13. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 zum Umwandeln von Wechselspannung
in Gleichspannung innerhalb der Prozessindustrie, wo die Vorrichtung als ein Magnetwiderstand-gesteuerter
variabler Transformator verwendet wird, bei dem die Ausgangsspannung proportional
zur Magnetwiderstandsänderung in einem Kern ist, der magnetisch parallel oder in Reihe
mit einem externen oder internen Kern mit einer getrennten sekundären Wicklung verbunden
ist und wo drei oder mehr solche Magnetwiderstand-gesteuerter Transformatoren mit
den bekannten Dreiphasengleichrichterverbindungen für 6- oder 12-Pulsgleichrichterverbindungen
für eine Diodenausgangsstufe verbunden sind.
14. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 in Gleichrichtern zum
Umwandeln von Wechselspannung in Gleichspannung zur Verwendung innerhalb der Prozessindustrie,
wobei die Vorrichtung Spannungsverbinder bildet, die als variable Induktionen in Reihe
mit den Primärwicklungen von bekannten Transformatorverbindungen verwendet werden,
und wo drei oder mehr solcher Transformatoren mit Dreiphasengleichrichterverbindungen
für 6 oder 12-Pulsgleichrichterverbindungen für eine Diodenausgangsstufe verbunden
sind.
15. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 für Gleichstrom/Wechselstrom-
oder Wechselstrom/Gleichstromwandler zur Verwendung auf dem Gebiet der Schaltnetzteile,
zur Verminderung der Größe des Magnetspannungswandlers, da die Vorrichtung einen Magnetwiderstand-gesteuerte
variablen Transformator bildet, wo die Ausgangsspannung proportional zur Magnetwiderstandsänderung
in einem Kern ist, der magnetisch parallel oder in Reihe mit einen externen oder internen
Kern mit einer getrennten Sekundärwicklung verbunden ist.
16. Verwendung eines Regulators gemäß Anspruch 15, dadurch gekennzeichnet, dass Filter, in denen eine Induktion einen Teil bildet, mit einer variablen Induktion
versehen sind.
17. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 als eine Komponente
in einem einstellbaren Spannungskompensator im Hochspannungsverteilernetzwerk, wo
die Vorrichtung lineare variable Induktion erzeugt.
18. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 als eine Komponente
in einem einstellbaren reaktiven Leistungskompensator (VAR-Kompensator), wobei die
Vorrichtung lineare variable Induktion in Verbindung mit bekannten Filterschaltungen
erzeugt, wo zumindest ein Kondensator ebenfalls als ein Element enthalten ist, wobei
die Vorrichtung in Form eines Magnetwiderstand-gesteuerten Transformators vorliegt,
der als ein Element in einer Kompensatorverbindung eingesetzt wird, wo die Kapazität
oder Induktion automatisch eingekoppelt und in dem Grad eingestellt werden, der zum
Kompensieren der reaktiven Leistung erforderlich ist.
19. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 in einem System zur
Magnetwiderstand-gesteuerten direkten Umwandlung einer Wechselspannung in eine Gleichspannung.
20. Verwendung eines Regulators gemäß einem der Ansprüche 1 bis 8 in einem System für
die Magnetwiderstand-gesteuerte Richtungsumwandlung einer Gleichspannung in eine Wechselspannung.
1. Régulateur de tension ou de courant influencé magnétiquement, comprenant:
un premier corps tubulaire externe (20) et un second corps tubulaire interne (21),
chacun d'entre eux est formé d'une matière magnétisable et fournit un circuit magnétique,
lesdits corps (20, 21) étant concentriques l'un par rapport à l'autre et ayant ainsi
un axe commun (A1),
au moins un premier conducteur électrique (8) bobiné autour des corps tubulaires (20,
21) en au moins une spire formant un premier enroulement principal (2) et au moins
un second conducteur électrique (9) fourni dans un entrefer (22) entre les corps (20,
21) et bobiné autour de l'axe commun (A1) du corps en au moins une spire formant un
second enroulement principal ou un enroulement de commande (4), ou
au moins un premier conducteur électrique (8) fourni dans un entrefer (22) entre les
corps (20, 21) et bobiné autour de l'axe commun (A1) des corps en au moins une spire
formant un premier enroulement principal (2) et au moins un second conducteur électrique
(9) bobiné autour des corps tubulaires (20, 21) en au moins une spire formant un second
enroulement principal ou un enroulement de commande (4),
où l'axe d'enroulement (A2) pour la spire ou les spires dans l'enroulement principal
(2) se situe à angle droit de l'axe d'enroulement (A4) pour la spire ou les spires
dans l'enroulement de commande (4) aux fins de fournir des champs magnétiques orthogonaux
(H1, B1 ; H2, B2) dans les corps et contrôlant ainsi le comportement de la matière
magnétisable par rapport au champ (H1, B1) dans l'enroulement principal (2) au moyen
du champ (H2, B2) dans l'enroulement de commande (4),
caractérisé en ce que
les premier et second corps sont formés d'un bobinage de matière magnétique, et
en ce que le régulateur fournit un circuit magnétique fermé pour les champs magnétiques orthogonaux
(H1, B1 ; H2, B2) au moyen desdits premier et second corps, d'un premier connecteur
de champ magnétique (10) et d'un second connecteur de champ magnétique (11), lesdits
premier et second connecteurs de champ magnétique interconnectant magnétiquement les
surfaces d'extrémité respectives des premier et second corps.
2. Régulateur selon la revendication 1, caractérisé en ce que les connecteurs de champ magnétique (10, 11) comprennent chacun un entrefer (13)
pour faciliter l'insertion du premier connecteur (8) ou du second connecteur (9) et
pour interrompre les lignes de force du champ magnétique H1 (B1) depuis le conducteur
(8, 9).
3. Régulateur selon la revendication 1 ou 2, caractérisé en ce qu'il comprend un troisième conducteur électrique (27) bobiné en une spire qui forme
un troisième enroulement principal (3), où l'axe d'enroulement (A3) pour la spire
ou les spires dans le troisième enroulement principal (3) coïncide avec, ou est parallèle
à, l'axe d'enroulement (A2) pour la spire ou les spires dans le premier enroulement
principal (2), offrant ainsi un effet de transformateur entre le premier enroulement
principal et le troisième enroulement principal lorsque au moins un d'entre eux est
excité.
4. Régulateur selon la revendication 1 ou 2, caractérisé en ce qu'il comprend un troisième conducteur électrique (27) bobiné en au moins une spire qui
forme un troisième enroulement principal (3), où l'axe d'enroulement (A3) pour la
spire ou les spires dans le troisième enroulement principal (3) coïncide avec, ou
est parallèle à, l'axe d'enroulement (A4) pour la spire ou les spires dans l'enroulement
de commande (4), offrant ainsi un effet de transformateur entre le troisième enroulement
principal (3) et l'enroulement de commande (4) lorsque au moins un d'entre eux est
excité.
5. Régulateur selon une quelconque des revendications 1 à 4, caractérisé en ce qu'il comprend un corps tubulaire supplémentaire qui fournit un noyau externe (25) qui
est monté à l'extérieur du premier corps tubulaire (20) externe, où les corps (20,
21, 25) sont concentriques les uns par rapport aux autres et ont ainsi un axe commun
(A1).
6. Régulateur selon la revendication 5, caractérisé en ce qu'il comprend un troisième conducteur électrique (27) bobiné autour du noyau externe
(25) en une spire qui forme un troisième enroulement principal (3), où l'axe d'enroulement
(A3) pour la spire ou les spires dans le troisième enroulement principal (3) coïncide
avec, ou est parallèle à, l'axe d'enroulement (A2) pour la spire ou les spires dans
le premier enroulement principal (2), offrant ainsi un effet de transformateur entre
le premier enroulement principal (2) et le troisième enroulement principal (3) lorsque
au moins un d'entre eux est excité, ou lorsque l'axe d'enroulement (A3) pour la spire
ou les spires dans le troisième enroulement principal (3) coïncide avec, ou est parallèle
à, l'axe d'enroulement (A4) pour la spire ou les spires dans l'enroulement de commande
(4), offrant ainsi un effet de transformateur entre le troisième enroulement principal
(3) et l'enroulement de commande, lorsque au moins un d'entre eux est excité.
7. Régulateur selon la revendication 5 ou 6, caractérisé en ce que le noyau externe (25) est composé de plusieurs parties annulaires (25', 25", etc.)
et en ce que le premier enroulement principal (2) et/ou le troisième enroulement principal (3)
forment des enroulements individuels autour de chaque partie annulaire.
8. Régulateur selon une quelconque des revendications 5 à 7, caractérisé en ce que le noyau externe (25) est composé de plusieurs parties annulaires (25', 25", etc.),
et en ce que l'enroulement de commande (4) et/ou le troisième enroulement principal (3) forment
des enroulements individuels autour de chaque partie annulaire.
9. Utilisation d'un régulateur selon une quelconque revendication précédente en tant
que composant d'un convertisseur de fréquence pour la conversion de la fréquence d'entrée
en fréquence de sortie sélectionnée de façon aléatoire, de préférence en vue du fonctionnement
d'un moteur asynchrone dans une connexion de cycloconvertisseur.
10. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 en tant
que connecteur d'un convertisseur de fréquence pour la conversion de la fréquence
d'entrée en fréquence de sortie sélectionnée de façon aléatoire, et en vue du fonctionnement
d'un moteur asynchrone, pour la sommation de parties de la tension par phase générée
à partir d'un transformateur à 6 ou 12 impulsions vers chaque phase moteur.
11. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 en tant
que convertisseur de courant continu en courant alternatif qui convertit la tension/le
courant à courant continu en tension/courant à courant alternatif d'une fréquence
de sortie sélectionnée de façon aléatoire, où l'énergie magnétique enregistrée dans
un premier enroulement principal alimenté en courant continu ou l'inductance d'un
enroulement primaire est variée au moyen d'un champ de commande orthogonale qui influence
l'inductance, générant ainsi une tension à courant alternatif dans le troisième enroulement
principal ou l'enroulement secondaire dans le connecteur de tension avec une fréquence
égale à la fréquence de la variation de flux/variation d'inductance.
12. Utilisation d'un régulateur selon la revendication 11, dans laquelle trois de ces
convertisseurs de tension d'inductance variable sont interconnectés afin de générer
une tension triphasée avec une fréquence de sortie sélectionnée de façon aléatoire
qui est connectée à ladite machine asynchrone.
13. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 pour la
conversion de tension à courant alternatif en tension à courant continu au sein de
l'industrie de fabrication, où le dispositif est utilisé comme un transformateur variable
commandé par réluctance dans lequel la tension de sortie est proportionnelle au changement
de réluctance dans un noyau qui est magnétiquement connecté en parallèle ou en série
à un noyau externe ou interne avec un enroulement secondaire séparé, et dans lequel
trois ou plus de ces transformateurs commandés par réluctance sont connectés aux connexions
connues de rectificateur triphasé pour des connexions de rectificateur à 6 ou 12 impulsions
pour l'étage de sortie de diode.
14. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 dans des
rectificateurs pour la conversion de tension à courant alternatif en tension à courant
continu pour l'utilisation dans l'industrie de fabrication, où le dispositif forme
des connecteurs de tension qui sont utilisés comme des inductances variables en série
avec les enroulements primaires sur les connexions de transformateur connues, et où
trois ou plus de ces transformateurs sont connectés aux connexions de rectificateur
triphasé pour des connexions de rectificateur à 6 ou 12 impulsions pour l'étage de
sortie de diode.
15. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 pour des
convertisseurs ca/cc ou cc/ca pour l'utilisation dans le domaine de l'alimentation
commutée, pour la réduction de la taille du convertisseur de tension magnétique, étant
donné que le dispositif forme un transformateur variable commandé par réluctance dans
lequel la tension de sortie est proportionnelle au changement de réluctance dans un
noyau qui est connecté magnétiquement en parallèle ou en série à un noyau externe
ou interne avec un enroulement secondaire séparé.
16. Utilisation d'un régulateur selon la revendication 15, caractérisé en ce que des filtres, dont une partie est formée par l'inductance, sont fournis avec une inductance
variable.
17. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 en tant
que composant d'un compensateur de tension réglable dans le réseau de distribution
haute tension, dans lequel le dispositif crée une inductance variable linéaire.
18. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 en tant
que composant d'un compensateur de puissance réactive réglable (compensateur VAR)
dans lequel le dispositif crée une inductance variable linéaire en lien avec des circuits
à filtre connus dans lesquels au moins un condensateur est également inclus comme
élément, le dispositif sous la forme d'un transformateur commandé par réluctance étant
utilisé comme un élément dans une connexion de compensateur dans lequel la capacité
d'inductance est automatiquement couplée et ajustée selon l'étendue nécessaire pour
compenser la puissance réactive.
19. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 dans un
système pour la conversion directe commandée par réluctance d'une tension à courant
alternatif en tension à courant continu.
20. Utilisation d'un régulateur selon une quelconque des revendications 1 à 8 dans un
système pour la conversion directe commandée par réluctance d'une tension à courant
continu en tension à courant altematif.