Technical Field
[0002] This disclosure relates to power supply systems, and more particularly, to circuitry
and methodology for controlling a DC/DC forward converter with active clamp reset.
Background Art
[0003] A DC/DC forward converter uses transformer windings to provide voltage conversion
and galvanic isolation for the load. Power converters based on a forward topology
are generally more efficient than flyback converters. By contrast with a flyback converter
that stores energy as a magnetic field in the inductor when the switching element
is conducting, a forward converter does not store energy in the transformer during
the conduction time of the switching element. Instead, energy is passed to the output
of the forward converter directly by transformer action during the switch conduction
phase. The operation of the transformer in a forward topology doesn't inherently self-reset
each power switching cycle. The transformer in a forward converter requires the application
of a mechanism to reset the transformer each power cycle. The active clamp reset mechanism
is presently finding extensive use.
[0004] FIG. 1 illustrates a conventional DC/DC forward converter 10 with an active clamp
reset that converts an input voltage Vin into an output voltage Vout that may be higher
or lower than the input voltage Vin. The converter 10 includes a power transformer
PT having primary and secondary windings. The primary side and secondary side of the
transformer PT may or may not be on opposite sides of an isolation barrier (i.e. referenced
to independent grounds). A primary gate PG and an active clamp gate AG are arranged
on the primary side of the transformer PT. A forward gate FG and a synchronous gate
SG are provided on the secondary side of the transformer PT. The AG, FG and SG may
be N-type MOSFETs, whereas the AG may be a P-type MOSFET.
[0005] The converter 10 further includes a clamp capacitor C
C arranged on the primary side of the transformer PT, and an inductor L and an output
capacitor C
OUT coupled on the secondary side of the transformer PT. The active clamp gate AG is
controlled using a level shift circuit including a capacitor C
1, a Schottky diode D and a resistor R.
[0006] FIG. 2 shows timing diagrams that illustrate operation of the forward converter 10.
A switching period of the forward converter 10 is defined by the period of a pulse
width modulation (PWM) signal that controls switching of the AG, PG, FG and SG in
the forward converter 10. The PWM period is composed of the on-time t
ON, and the core reset time required to reset the magnetic flux in the transformer core.
The reset is performed when the AG is on. When the PWM signal goes high, the AG is
turned off as represented by the rising edge on the AG timing diagram. In a DC/DC
Forward Converter with Active Clamp Reset, it is commonly known that setting a delay
between the turn-off of the AG and the turn-on of the PG decreases power loss due
to switching the PG with lower drain-source voltage. To minimize power loss, the PG
is turned on only after the potential at the SWP node coupled to the drain of the
PG falls from a voltage of Vin/(1-D) to the input voltage Vin, where D is a duty cycle
of the converter 10. The Vin/(1-D) voltage corresponds to the voltage at the fully
charged clamp capacitor C
C. The time for the potential at the SWP node to fall is a function of the magnetizing
current of the power transformer PT and the capacitance of the PG and AG, and generally
is in the range from 200 ns to 1 µs.
[0007] On the secondary side, the FG is turned on also after a delay. The SG and the FG
are configured as make-before-break, so the SG is on (a high level on the SG timing
diagram) until the FG turns on. After the FG turns on (the rising edge on the FG timing
diagram), the SG turns off (the falling edge on the SG timing diagram). If the FG
and the SG switch immediately when the AG turns off, significant power will be lost
in the body diode of the SG. If the FG and the SG switch after the PG turns on, then
the SG and the PG will be cross-conducting and will lose power due to shoot-through.
Therefore, the FG delay from the time when the AG turns off to the time when the FG
turns on must be shorter than the PG delay from the time when the AG turns off to
the time when the PG turns on, but not short enough to lose significant power in the
body diode of the SG.
[0008] As indicated above, the PG delay can be up to 1 µs in some cases. While this delay
is good for efficiency, power is not transferred from the primary side to the secondary
side during this time. Therefore, the PG delay limits the maximum achievable duty
cycle of the converter 10. Generally, in single switch forward converters, the duty
cycle is already limited to between 65% and 80% to allow sufficient "off" time for
the active clamp to reset the magnetic flux in the transformer core. The extra delay
before turning on the PG further reduces this duty cycle. With a common switching
frequency of 200kHz, the maximum achievable duty cycle could be lower than 50% for
a 1 µs delay. The need for higher duty cycles in active clamp reset forward converters
is becoming more common as input ranges are extending from a ratio of 1:2 for a 36V-72V
system to 1:4 for a 9V-36V system, or even higher.
[0009] If the system requires a wide input range, the design can usually be modified to
be made to work However, there is a huge compromise in component selection. For example,
consider a 9V-36V system with a 200kHz switching frequency, 1µs delay, and 70% maximum
duty cycle. In this case, the maximum achievable duty cycle is 50%. Therefore, the
transformer turns ratio could be selected such that when Vin is 9V a 50% or lower
duty cycle can be achieved. This will result in a non-optimal turns ratio for power
loss in the transformer. Additionally, this higher turns ratio presents higher voltage
stress on the MOSFETs, particularly when Vin is 36V.
[0010] A competent power supply designer would not choose the turns-ratio based on the 1µs
delay setting, as it would cause more power loss than it saves. Therefore, the designer
would simply reduce the delay setting to achieve the required duty cycle, and the
power loss due to switching the PG would not be minimized.
[0011] Hence, there is a need for a technique that would allow the achievable duty cycle
of a forward converter with an active clamp reset to be extended so as to minimize
power loss.
Summary of the Disclosure
[0012] The present disclosure offers a novel system and methodology for controlling a DC/DC
forward converter with active clamp reset. In accordance with one aspect of the disclosure,
a system is configured for controlling a DC/DC forward converter having a transformer
with primary and secondary windings, a reset switch, and a first switch coupled to
the primary winding of the transformer. The control system comprises a PWM control
circuit responsive to an output signal of the converter for producing a PWM signal
to control switching of the reset switch and the first switch. A period of the PWM
signal includes an on-time interval for enabling transfer of power via the transformer
when the first switch is on, and a reset time interval for enabling reset of the transformer
when the reset switch is on. A maximum value of the on-time interval is pre-set to
provide sufficient time for the reset. The reset switch is turned off when the PWM
signal goes from a first level to a second level. A first delay period is set between
time when the reset switch turns off and time when the first switch turns on. A first
delay control circuit is provided for reducing the first delay period when the on-time
interval approaches the maximum value.
[0013] Further, the converter may include a second switch coupled to the secondary winding
of the transformer. A second delay period shorter than the first delay period may
be set between the time when the reset switch turns off and the time when the second
switch turns on. A second delay control circuit may be provided for reducing the second
delay period when the on-time interval approaches the maximum value.
[0014] The first delay control circuit may be configured to determine a. difference Δt between
duration of the on-time interval and the maximum value of the on-time interval, and
to reduce the first delay period to a value of (m x Δt) if the value of (m x Δt) is
less the first delay period, where m is a constant value selected to provide stability
of converter operations.
[0015] The second delay control circuit may be configured to determine the difference Δt
between duration of the on-time interval and the maximum value of the on-time interval,
and to reduce the second delay period to a value of (k x Δt), if the value of (k x
Δt) is less than the second delay period, where k is a constant value selected to
provide stability of converter operations, and m exceeds k.
[0016] For example, the first delay control circuit may include a first timing capacitor,
a first current source for producing a first value of current representing the first
delay period, and a second current source for producing a second value of current
proportional to the first value. The first timing capacitor may be coupled to the
first and second current sources so as to be charged with current of the first value
and discharged with current of the second value.
[0017] Also, the first delay control circuit may include a comparator for comparing voltage
at the first timing capacitor with a threshold value to control charging of the first
timing capacitor. The first timing capacitor may be disconnected from the first current
source when the voltage at the first timing capacitor reaches the threshold value.
[0018] The first timing capacitor may be connected to the first current source for charging
when the PWM signal goes to the second level, and may be connected to the second current
source for discharging when the PWM signal goes to the first level. The first timing
capacitor may be disconnected from the second current source in response to the maximum
value of the on-time interval.
[0019] Similarly, the second delay control circuit may include a second timing capacitor,
a third current source for producing a third value of current representing the second
delay period, and a fourth current source for producing a fourth value of current
proportional to the third value, where the fourth value is higher than the second
value. The second timing capacitor may be coupled to the third and fourth current
sources so as to be charged with current of the third value and discharged with current
of the fourth value.
[0020] In accordance with another aspect of the disclosure, a duty cycle range is extended
in a DC/DC forward comparator having a transformer with primary and secondary windings,
a reset switch, and a first switch coupled to the primary winding of the transformer.
The duty cycle range extension method involves the step of producing a PWM signal
to control switching of the reset switch and the first switch, based on an output
signal of the converter. A period of the PWM signal includes an on-time interval for
enabling transfer of power via the transformer when the first switch is on, and a
reset time interval for enabling reset of the transformer when the reset switch is
on. A maximum value of the on-time interval is pre-set to provide sufficient time
for the reset. The reset switch is turned off when the PWM signal goes from a first
level to a second level. A first delay period is set to delay turn-on of the first
switch after the reset switch turns off, thereby reducing a duty cycle of the converter.
The first delay period is reduced when the on-time interval approaches the maximum
value, so as to extend the duty cycle.
[0021] Also, the converter may include a second switch coupled to the secondary winding
of the transformer. A second delay period shorter than the first delay period may
be set to delay turn-on of the second switch after the reset switch turns off. The
second delay period may be reduced when the on-time interval approaches the maximum
value, so as to further extend the duty cycle.
[0022] The step of reducing the first delay period may comprise:
- in a first switching cycle of the converter, determining a difference Δt between duration
of the on-time interval and the maximum value of the on-time interval, and
- in a second switching cycle of the converter carried out after the first switching
cycle, reducing the first delay period to a value of (m x Δt) if the value of (m x
Δt) is less the first delay period, where m is a constant value selected to provide
stability of converter operations.
[0023] The step of reducing the second delay period may comprise:
- in a first switching cycle of the converter, determining a difference Δt between duration
of the on-time interval and the maximum value of the on-time interval, and,
- in a second switching cycle of the converter carried out after the first switching
cycle, reducing the second delay period to a value of (k x Δt), if the value of (k
x Δt) is less than the second delay period, where k is a constant value selected to
provide stability of converter operations, and m exceeds k.
[0024] Additional advantages and aspects of the disclosure will become readily apparent
to those skilled in the art from the following detailed description, wherein embodiments
of the present disclosure are shown and described, simply by way of illustration of
the best mode contemplated for practicing the present disclosure. As will be described,
the disclosure is capable of other and different embodiments, and its several details
are susceptible of modification in various obvious respects, all without deporting
from the spirit of the disclosure. Accordingly, the drawings and description are to
be regarded as illustrative in nature, and not as limitative.
Brief Description of the Drawings
[0025] The following detailed description of the embodiments of the present disclosure can
best be understood when read in conjunction with the following drawings, in which
the features are not necessarily drawn to scale but rather are drawn as to best illustrate
the pertinent features, wherein:
[0026] FIG. 1 is a diagram illustrating a typical arrangement of a DC/DC forward converter
with active clamp reset.
[0027] FIG. 2 shows timing diagrams that illustrate switching of the gates in the DC/DC
forward converter with active clamp reset.
[0028] FIG. 3 shows timing diagrams that illustrate the concept of the duty cycle range
extension in accordance with the present disclosure.
[0029] FIG. 4 illustrates relative timing between switching of the primary gate (PG) and
the forward gate (FG) in accordance with the present disclosure.
[0030] FIG. 5 schematically illustrates an exemplary embodiment of the duty cycle range
extension in accordance with the present disclosure.
[0031] FIG. 6 is a circuit diagram illustrating an exemplary embodiment of the FG delay
control circuitry in accordance with the present disclosure.
[0032] FIG. 7 shows timing diagrams illustrating the FG delay control in accordance with
the present disclosure.
[0033] FIG. 8 is a circuit diagram illustrating an exemplary embodiment of the FG and PG
delay control circuitry in accordance with the present disclosure.
Detailed Disclosure of the Embodiments
[0034] The present disclosure will be made using an example of a peak current mode control
in a forward converter with active clamp reset. It will become apparent, however,
that the concepts described herein are applicable to any method of controlling a forward
converter with active clamp reset.
[0035] FIG. 3 illustrates the concept of extending achievable duty cycle of a forward converter
with active clamp reset in accordance with the present disclosure. The on-time t
ON in FIG. 3 indicates an actual on-time of a PWM control signal in a current cycle
of the convener. The maximum on-time t
MAX defines the maximum on-time value of the PWM control signal to provide sufficient
core reset time to reset the transformer. Further, the user may program the respective
delay time T
DELAY that defines a delay from the time when the active clamp gate AG turns off to the
time when the primary gate PG or the forward gate FG turns on.
[0036] As the on-time t
ON of the PWM control-signal in a current switching cycle approaches the maximum on-time
value T
MAX, the difference between these two time intervals is measured as Δt
1, = t
MAX - t
ON. For the next switching cycle, the delay time t
D between turning off of the AG and turning on of the PG or FG is then set equal to
the lesser of T
DELAY and k*Δt
1, where k is a constant value selected to guarantee stability of the converter operation.
For example, k may be in the range from 0.9 to 1.1. In the cycle, in which the on-time
t
ON becomes equal to the maximum on-time t
MAX, the delay time t
D is equal to zero, and the full maximum duty cycle is achieved.
[0037] In a forward converter with active clamp reset, the synchronous gate SG must turn
off before the primary gate PG turns on to avoid shoot through. The forward gate FG
and the synchronous gate SG are make-before-break, so the FG must turn on before the
PG turns on. Therefore, as shown in FIG. 4, the delay time t
DELAY(FG) before the FG turns on must be less than the delay time t
DELAY(PG) before the PG turns on, to avoid shoot-through. If only the PG delay were reduced
as t
ON approaches t
MAX, then the PG would turn on before the FG, and the SG and PG shoot-through would occur.
Thus, the FG delay must also be reduced as t
ON approaches T
MAX. Furthermore, if the FG and the PG delays were limited to the same value Δt1 = t
MAX - t
ON, then the FG and the PG would be transitioning at the same time, which may cause
shoot-through due to propagation delays and rise times. As shown in FIG. 4, to avoid
this problem, the reduced delay time t
n1 for the PG may be made longer than the reduced delay time t
D2 for the FG. For example, the PG delay time t
D1 may be equal to 1.1*k*Δtl when the FG delay time t
D2 is k*Δt1. In this manner, the PG delay time will be 10% longer than the FG delay
time as t
ON approaches t
MAX.
[0038] FIG. 5 that schematically illustrates the concept of extending achievable duty cycle
in accordance with the present disclosure, shows a pin (PTN) of the converter controller
IC that sets the delay time T
DELAY programmable by the user. The delay time t
DELAY may be set using a resistor R
DELAY, value of which is selected by the user. The resistor R
DELAY defines the value of the delay current I
DELAY that flows between a reference voltage source V
REF and the pin. As shown in more detail later, the user-programmable delay time t
DELAY is reduced using a circuit including current sources A1 and A2 coupied to a timing
capacitor Cr via switches S1 and S2, and a delay comparator A3 that compares the capacitor
voltage VCAP (voltage at the node VCAP shown in FIG. 5) with a threshold voltage V
TH. The switch S is closed when the PWM signal goes high, and is opened in response
to an output signal of the comparator. The switch S2 is closed when the PWM signal
goes low, and is open when the maximum on-time t
MAX is reached.
[0039] In particular, FIG. 6 shows an exemplary embodiment of a system that controls a DC/DC
forward converter 100 with active clamp reset so as to reduce the FG delay as the
PWM on-time t
ON approaches the PWM maximum on-time value t
MAX. The DC/DC forward converter 100 converts an input voltage Vin into an output voltage
Vout that may be higher or lower than the input voltage Vin. The converter 100 includes
a power transformer PT having primary and secondary windings. A primary gate PG and
an active clamp gate AG are coupled to the primary winding of the transformer PT.
A forward gate FG and a synchronous gate SG are coupled to the secondary winding of
the transformer PT. The AG, FG and SG may be N-type MOSFETs, whereas the AG may be
a P-type MOSFET. The converter 100 further includes a clamp capacitor C
C arranged on the primary side of the transformer PT, and an inductor L and an output
capacitor C
OUT coupled on the secondary side of the transformer PT. A level, shift required for
controlling a p-type MOSFET of the AG is provided using a level shift circuit including
a capacitor C
1, a Schottky diode D and a resistor R.
[0040] An exemplary converter control circuit 102 in FIG. 6 controls the converter 100 in
a peak current control mode. However, as one skilled in the art would realize, the
technique for extending achievable duty cycle of the present disclosure is applicable
to any converter control mode. The converter control circuit 102 includes a clock
104 that produces a PWM clock which determines when the power transfer cycle should
start. Also, the clock 104 produces a maximum duty cycle signal MAX DUTY which determines
the maximum on-time value t
MAX. For example, the maximum duty cycle signal may set the maximum on-time t
MAX at about 70% of the converter period.
[0041] On the rising edge of the PWM clock, an RS latch 106 is set. As a result; the PWM
control signal produced at the output of the latch 106 goes high. The output of the
latch 106 is coupled to inputs of AND gates 108 and 110, and via an inverter to the
S input of a reset dominant latch 112. The output of the AND gate 110 controls a switch
S1 coupled to a current source A1. The output of the latch 112 controls a switch S2
coupled to a current source A2. The current source A1 produces the I
DELAY current that may correspond to the current defining the user-programmable delay time
T
DELAY. The current source A2 produces the current of the K*I
DELAY value, where k is a constant that may be selected, for example, in the range from
0.9 to 1.1. A timing capacitor C
T is coupled via the switches S1 and S2 to the current sources A1 and A2, respectively.
A delay comparator 114 is provided to compare the voltage at the VCAP node with a
threshold voltage V
TH that may be selected based on circuit considerations to support adequate switching
of the gates in the converter 100. The comparator 114 may be a hysteresis comparator.
[0042] When the output of the delay comparator 114 is low the switch S1 is turned on, through
the AND gate 110, and the delay current I
DELAY from the current source A1 is transferred to the timing capacitor C
T. The value of the delay current I
DELAY may be programmable using the delay resistor R
DELAY (shown in FIG. 5) to define a desired delay for the FG turn on.
[0043] The current source A1 creates a linear voltage ramp on the capacitor C
T, which increases until the VCAP voltage reaches the threshold value V
TH, at which time the delay comparator 114 trips and performs two functions. First,
it turns off the switch S 1 through the AND gate 110. Second, it allows the output
of the AND gate 108 to go high provided that the PWM signal is still at a high level.
Thus, the FG controlled by the output signal of the AND gate 108 is turned on and,
via an inverter 116, the SG is turned off by a delayed PWM signal.
[0044] At this time, provided that the PG is also ON, power is transferred from the input
Vin to the output Vout. The voltage across the power transformer PT causes the current
in the inductor L to linearly increase. An error amplifier 118 is coupled to the output
Vout via a resistor divider composed of resistors R
1 and R
2 to compare a voltage representing the output current of the converter 100 with a
reference voltage VREF
0. The capacitor C
2 is coupled to the error amplifier 118 to provide signal integration. An error signal
produced at the output of the error amplifier 118 is supplied to a current comparator
120 that compares the error signal with the inductor current.
[0045] When the inductor current reaches a threshold determined by the error signal, the
current comparator 120 trips. The output of the comparator 120 resets the latch 106
and causes the PWM signal at the output of the latch 106 to go low. When the PWM signal
goes low, the RS latch 112 is set and its output Q goes high. This turns on the switch
S2 which linearly discharges the voltage VCAP on the-capacitor C
1. The latch 112 is reset on the rising edge of the MAX DUTY signal produced by the
clock 104. Any residual voltage V
RES remaining on the capacitor C
T translates into a time value that is subtracted from the delay time in the next cycle
when the PWM clock goes high.
[0046] Accordingly, as illustrated in FIG. 7, in the initial charge phase when the timing
capacitor C
T is fully discharged, switch S1 closes at the PWM signal rising edge, and the current
I
DELAY from the current source A1 causes a linear voltage ramp of the VCAP voltage from
0V to a threshold voltage V
TH. When the VCAP voltage reaches the threshold value V
TH, the delay comparator 114 trips. The time that it takes to ramp the capacitor voltage
VCAP from 0V to the threshold value V
TH corresponds to the user-programmed delay time t
DELAY. The logic turns on the gate FG and opens the switch S1. At this time, both switches
S1 and S2 are open, and VCAP=V
TH.
[0047] In the discharge phase, the switch S2 closes when the PWM signal goes low (at t
ON), and opens when the maximum duty cycle is reached (at t
MAX). When the S2 is closed, current source A2 pulls off the current equal to k*I
DELAY of the capacitor C
T, which linearly decreases the VCAP voltage. When the maximum duty cycle is reached,
S2 opens.
[0048] At this time, VCAP=V
TH-[k*I
DELAY/C
T*(t
MAX-t
ON)]. Both switches remain open until the next charge cycle. The VCAP voltage is limited
to 0V on the discharge cycle. If t
ON is close to t
MAX, then a residual voltage V
RES having a value between 0V and V
TH will be left on the capacitor C
T.
[0049] In the next converter cycle defined by the rising edge of the PWM clock, if t
ON was close to t
MAX in the previous cycle; there is a residual voltage V
RES left on the capacitor C
T equal to V
TH-[k*I
DELAY/C
T*(t
MAX-t
ON)]. When the switch S1 is closed again, current is sourced into the capacitor C
T. The time during which the VCAP voltage ramps from the level of V
TH-[k*I
DELAY/C
T*(t
MAX-t
ON)] to the V
TH level is equal to k*(t
MAX-t
ON). Therefore, the FG delay t
D2 for the new cycle is k*(t
MAX-t
ON).
[0050] Hence, as illustrated in FIG. 7, when the on-time t
ON defined by the PWM signal at the output of the latch 106 approaches the maximum on-time
t
MAX defined by the max duty signal, the difference Δt
1 between the t
MAX and t
ON corresponds to a time interval determined by the fall of the capacitor voltage VCAP
from the V
TH level to the V
RES level, i.e. until the maximum on-time t
MAX is reached. As a result, the FG delay time t
D2 in the next cycle of the converter is determined by a time interval defined by the
rise of the VCAP voltage from the V
RES level to the V
TH level, which is less than the initial FG delay time t
DELAY defined by the rise of the VCAP from 0V to the V
TH level.
[0051] FIG. 8 illustrates an exemplary embodiment of a system 200 for controlling a DC/DC
forward converter 100 with active clamp reset so as to reduce the PG delay in addition
to the FG delay. The converter control system 200 includes a forward converter control
loop 202, a secondary side delay control circuit 204 and a primary side delay control
circuit 206. The forward converter control loop 202 includes the clock 104, the latch
106, the error amplifier 118 with the capacitor C2, and the current comparator 120.
These elements are similar to the respective elements in FIG. 6 and operate in a similar
manner.
[0052] The secondary side delay control circuit 204 include the AND gates 108 and 110, the
reset dominant latch 112, the delay comparator 114, timing capacitor C
T1, switches S1 and S2, and current sources A and A2 that produce currents I
DELAY1 and k*I
DELAY1, respectively. These elements are similar to the respective elements in FIG. 6 and
operate in a similar manner.
[0053] The primary side delay control circuit 206 is provided to control the PG delay in
a manner similar to controlling the FG delay discussed in connection with the circuit
in FIG. 6. The primary side delay control circuit 206 includes AND gates 208 and 210,
a reset dominant latch 212, a delay comparator 214, a timing capacitor C
T2, switches S10 and S20, and current sources A 10 and A20 that produce currents I
DEIAY2 and 1.1*k*I
DELAY2, re9peeCivety, The primary gate PG is controlled by a signal at the output of the
AND gate 208. Also, when the PWM signal at the output of the latch 106 goes high,
this signal via an AG control circuit 220 turns off the active clamp gate AG.
[0054] The elements in the primary side delay control circuit 206 are similar to the respective
elements in the secondary side delay control circuit 204 and operate in a similar
manner. However, as previously mentioned, the primary gate PG must turn on after the
forward gate FG turns ON. Therefore, the current value. 1.1*k*I
DELAY2 produced by the current source A20 for discharging the primary side timing capacitor
C
T2 is larger than the discharging current k*I
DELAY1 in the secondary side delay control circuit 204 to ensure that the PG turn-on delay
is always longer than the FG turn-on delay when t
on is close to t
MAX. The value of the delay current I
DELAY2 in the primary side delay control circuit 206 may be equal to the value of the delay
current I
DELAY1 in the secondary side delay control circuit 204. Alternatively, the PG and FG delay
control may be provided using different values I
DELAY1 and I
DELAY2. Further, the threshold voltage V
TH1 applied in the secondary side delay control circuit 204 may be equal to threshold
voltage V
TH2 the primary side delay control circuit 206. Alternatively, the PG and FG delay control
may be provided using different threshold values V
TH1 and V
TH2.
[0055] The foregoing description illustrates and describes aspects of the present invention.
Additionally, the disclosure shows and describes only preferred embodiments, but as
aforementioned, it is to be understood that the invention is capable of use in various
other combinations, modifications, and environments and is capable of changes or modifications
within the scope of the inventive concept as expressed herein, commensurate with the
above teachings, and/or the skill or knowledge of the relevant art. For example, the
present disclosure is applicable to a DC/DC forward converter with active clamp reset,
where the converter is provided with primary side control instead of secondary side
control. Such a converter may include a primary gate PG, an active clamp gate AG,
and diodes provided on the secondary side of the transformer PT in place of the forward
gate FG and the synchronous gate SG.
[0056] The embodiments described hereinabove are further intended to explain-best modes
known of practicing the invention and to enable others skilled in the art to utilize
the invention in such, or other, embodiments and with the various modifications required
by the particular applications or uses of the invention.
[0057] Accordingly, the description is not intended to limit the invention to the form disclosed
herein. Also, it is intended that the appended claims be construed to include alternative
embodiments.
1. A system for controlling a DC/DC forward converter having a transformer with primary
and secondary windings, a reset switch, and a first switch coupled to the primary
winding of the transformer, the system comprising:
a PWM control circuit responsive to an output signal of the converter for producing
a PWM signal to control switching of the reset switch and the first switch,
a period of the PWM signal including an on-time interval for enabling transfer of
power via the transformer when the first switch is on, and a reset time interval for
enabling reset of the transformer when the reset switch is on,
a maximum value of the on-time interval being pre-set to provide sufficient time for
the reset,
the reset switch being turned off when the PWM signal goes from a first level to a
second level,
a first delay period being set between time when the reset switch turns off and time
when the first switch turns on; and
a first delay control circuit for reducing the first delay period when the on-time
interval approaches the maximum value.
2. The system of claim 1, further comprising a second switch coupled to the secondary
winding of the transformer, wherein a second delay period shorter than the first delay
period being set between time when the reset switch turns off and time when the second
switch turns on, the system further comprising a second delay control circuit for
reducing the second delay period when the on-time interval approaches the maximum
value.
3. The system of claim 1 or 2, wherein the first delay control circuit is configured
to determine a difference Δt between duration of the on-time interval and the maximum
value of the on-time interval, and to reduce the first delay period to a value of
(m x Δt) if the value of (m x Δt) is less the first delay period, where m is a constant
value selected to provide stability of converter operations.
4. The system of claim 2 or 3, wherein the second delay control circuit is configured
to determine the difference Δt between duration of the on-time interval and the maximum
value of the on-time interval, and to reduce the second delay period to a value of
(k x Δt), if the value of (k x Δt) is less than the second delay period, where k is
a constant value selected to provide stability of converter operations, and m exceeds
k.
5. The system of any one of claims 1 to 4, wherein the first delay control circuit includes
a first timing capacitor, a first current source for producing a first value of current
representing the first delay period, and a second current source for producing a second
value of current proportional to the first walue,wherein the first timing capacitor
being exemplarily coupled to the first and second current sources so as to being charged
with current of the first value and discharged with current of the second value.
6. The system of claim 5, wherein the first delay control circuit further includes a
comparator for comparing voltage at the first timing capacitor with a threshold value
to control charging of the first timing capacitor.
7. The system of claim 5 or 6, wherein the first timing capacitor is disconnected from
the first current source when the voltage at the first timing capacitor reaches the
threshold value.
8. The system of any one of claims 5 to 7, wherein the first timing capacitor is connected
to the first current source for charging when the PWM signal goes to the second level.
9. The system of any one of claims 5 to 8, wherein the first timing capacitor is connected
to the second current source for discharging when the PWM signal goes to the first
level.
10. The system of any one of claims 5 to 9, wherein the first timing capacitor is disconnected
from the second current source in response to the maximum value of the on-time interval.
11. The system of any one of claims 5 to 10, wherein the second delay control circuit
includes a second timing capacitor, a third current source for producing a third value
of current representing the second delay period, and a fourth current source for producing
a fourth value of current proportional to the third value, the fourth value is higher
than the second value,
wherein the second timing capacitor being exemplarily coupled to the third and fourth
current sources so as to being charged with current of the third value and discharged
with current of the fourth value.
12. A method of extending a duty cycle range in a DC/DC forward converter having a transformer
with primary and secondary windings, a reset switch, and a first switch coupled to
the primary winding of the transformer, the method comprising the steps of:
based on an output signal of the converter, producing a PWM signal to control switching
of the reset switch and the first switch;
a period of the PWM signal including an on-time interval for enabling transfer of
power via the transformer when the first switch is on, and a reset time interval for
enabling reset of the transformer when the reset switch is on,
a maximum value of the on-time interval being pre-set to provide sufficient time for
the reset,
the reset switch being turned off when the PWM signal goes from a first level to a
second level,
a first delay period being set to delay turn-on of the first switch after the reset
switch turns off, thereby reducing a duty cycle of the converter; and
reducing the first delay time when the on-time interval approaches the maximum value,
so as to extend the duty cycle.
13. The method of claim 12, wherein the converter further includes a second switch coupled
to the secondary winding of the transformer, and a second delay period shorter than
the first delay period being set to delay turn-on of the second switch after the reset
switch turns off, the method further comprising a step of reducing the second delay
time when the on-time interval approaches the maximum value, so as to further extend
the duty cycle.
14. The method of claim 12 or 13, wherein the step of reducing the first delay period
comprises:
in a first switching cycle of the converter, determining a difference Δt between duration
of the on-time interval and the maximum value of the on-time interval, and
in a second switching cycle of the converter carried out after the first switching
cycle, reducing the first delay period to a value of (m x Δt) if the value of (m x
Δt) is less the first delay period, where m is a constant value selected to provide
stability of converter operations.
15. The method of claim 13 or 14, wherein the step of reducing the second delay period
comprises:
in a first switching cycle of the converter, determining the difference Δt between
duration of the on-time interval and the maximum value of the on-time interval, and
in a second switching cycle of the converter carried out after the first switching
cycle, reducing the second delay period to a value of (k x Δt), if the value of (k
x Δt) is less than the second delay period, where k is a constant value selected to
provide stability of converter operations, and m exceeds k.