Field of the Invention
[0001] This invention relates to method of controlling loads under mains-dimmers, and to
power convertors configured to operate according to such methods.
Background of the Invention
[0002] Mains-dimmers are widely used for lighting applications. The most common type of
mains dimmer is the phase-cut dimmer, which relies on the generally sinusoidal cyclic
characteristic of the mains voltage signal, and disables the supply during a part
of the mains phase.
[0003] Apart from minor problems of flickering at very high dimming levels (that is to say,
low output levels, at which the power is significantly reduced) phase-cut dimmers
operate effectively for incandescent lighting. However other forms of lighting, such
as CFL (compact fluorescent lighting) or LED (light emitting diode) lighting generally
require relatively complex control and driver circuitry since they generally are high
impedance loads, in contrast to the low impedance characteristic of incandescent lighting.
They are thus typically not compatible with phase-cut dimmers.
[0004] Phase-cut dimmers are either "leading-edge" or "trailing edge", depending on which
part of the mains half-cycle is cut. Leading-edge dimmers are typically implemented
using a triac as the switching device, and trailing edge dimmers using a transistor
such as a MOS transistor. In the case of a leading edge dimmer, a firing network inside
the dimmer senses the mains voltage and fires at the appropriate phase angle of the
mains voltage. At the firing moment, the switching device is triggered. Provided that
sufficient current remains flowing in the triac (in the case of a leading edge dimmer)
after it is fired and it starts conducting, it stays in a conducting mode until the
next zero-crossing of the mains current. Such leading-edge dimmers therefore need
a minimum current to be drawn in order to prevent them turning off too early. This
current may be referred to as the holding current
[0005] Since high efficiency forms of lighting, such as CFL and LED require less power than
equivalent incandescent lighting, at deep dimming levels, the current drawn by the
lighting application may become so low that it is not able to keep the dimmer conducting
once the triac has fired. In known CFL and SSL systems, the load is configured to
draw an additional current, which may be 10 - 50 mA for a typical domestic wall-mounted
dimmer, by means of a bleed resistor in order to keep the dimmer conducting. This
current is not useful for providing luminosity and thus significantly decreases the
system's efficiency especially at low lighting levels.
[0006] A further problem arises for CFL and LED lighting applications, in that the firing
network requires a voltage across the dimmer in order to generate the proper firing
pulse. If the load is too small or completely absent, the voltage across the dimmer
becomes insufficient to trigger the firing correctly, which results in either firing
at an increased angle or not firing at all. A minimum current is therefore required
to be drawn by the load in order to supply the firing network - this current, of the
order of a few milliamps, is normally provided by a second bleeder resistor, which
acts to further reduce the operational efficiency.
[0007] The effects of the bleeder resistors are accentuated at very deep dimming levels
where only very low currents are drawn; they are even more significant for smart lighting
applications when in standby mode, at which times it is important to keep the power
drawn to a minimum in order to preserve the time for which the device can remain in
standby.
Summary of the invention
[0008] According to a first aspect of the invention there is provided a method of managing
the supply of power to a load from a phase-cut AC supply over a plurality of AC supply
half-cycle periods, the method comprising: drawing energy from the phase-cut AC supply
during at least one part of a first interval, the first interval being at least part
of at least one AC supply half-cycle; storing some of the energy, and supplying the
some of the energy to the load during a second interval being at least one subsequent
AC supply half-cycle; wherein the first and second intervals total to the plurality
of AC supply half-cycle periods. The power drawn from the AC supply, during the at
least one part of a first interval may thus be higher than it would be absent the
second interval during which power is not drawn. The load may be disconnected from
the supply during the second interval. Without restricting the inventing thereto,
it is noted that in applications with high impedance loads, such as CFL or LED lighting
application, it may be possible to reduce or even eliminate the losses associated
with bleeders thereby. The term 'plurality' includes a whole number, that is to say
'a plurality' includes 'an integral plurality'; however, it also includes a non-integral
number, that is to say, plurality includes for instance two-and-a-half. In the case
that the first and second intervals total to the plurality of AC supply half-cycle
periods, which plurality is non-integral (for instance, two-and-a-third half-cycles)
there may be a delay between the end of the second interval and start of the next
subsequent first interval, such that that first interval starts at a zero-crossing
of the AC supply. In embodiments, the method further comprises setting a duration
of at least one of the first interval and the second interval such that the power
drawn during the at least part of the first interval is sufficient to enable triggering
of the AC phase-cutting device. The AC phase-cutting device is the device which cuts
the phase of the AC supply, and may, for instance, be a triac or a transistor, and
may cut the leading edge or the trailing edge of the AC-phase. In the case of a leading-edge
phase-cut AC supply, the supply is switched on or triggered at the leading edge; in
the case of a trailing edge phase-cut supply, the supply is triggered or switched
on at the start of the phase. It may be possible to reduce or even eliminate the need
for a bleeder, which might otherwise be required to ensure correct triggering and/or
operation of the phase-cutting switch.
[0009] In embodiments the first interval is an AC supply half-cycle and the at least part
of a first interval comprises a single window.
[0010] In other embodiments the first interval is a plurality of AC supply half-cycles,
and the at least part of a first interval comprises a single window in each of the
plurality of AC supply half-cycles. In embodiments, the method may further comprise
detecting a phase of the AC supply, and synchronising the or each window to the phase
of the AC supply.
[0011] In embodiments, detecting a phase of the AC supply comprises detecting a zero-crossing
of the mains, and the method further comprises predicting a further zero-crossing
based on the detected zero-crossing.
[0012] In embodiments, the first and second intervals total to an odd-number of AC supply
half-cycles. Generation of harmonics of the mains frequency are generally undesirable,
and in some environments may be limited by regulations. In particular, even harmonics
(with a frequency twice, four times, six times, etc. the fundamental) are often undesirable
By requiring the total of the first and second interval to be an odd number of half-cycles,
that is to say, by requiring the sub-cycling to be over an odd number of half-cycles,
even- order harmonics may be reduced or even eliminated. It will be appreciated that
elimination of harmonics may not be necessary, or may be necessariy to only a lesser
extent, particularly in cases such as standy-by modes for smart lighting,
[0013] In embodiments, the at least one part of a first interval is one part of a first
interval and is shorter than a conduction angle of the phase-cut AC supply. Such embodiments
may reduce or avoid the requirement for or the size of, a bleeder circuit, even when
the energy which is required to be drawn from the AC supply is very low.
[0014] According to another aspect there is provided a controller for supplying power to
a load from a phase-cut AC supply over an integral plurality of AC supply half-cycle
periods, the controller being connectable to an energy store, the controller being
configured to: draw energy from the phase-cut AC supply during at least one part of
a first interval, the first interval being at least part of at least one AC supply
half-cycle, store some of the energy in the energy store and supply the some of the
energy to the load during a second interval being at least one subsequent AC supply
half-cycle, wherein the first and second interval total to the integral plurality
of AC supply half-cycle periods.
[0015] In embodiments the energy store is a capacitor.
[0016] In embodiments, the controller further comprises a zero-crossing detection unit.
It may further comprise a zero-crossing prediction unit.
[0017] According another aspect, there is provided a lighting control circuit comprising
a switched mode power converter and a controller as just described, and according
to yet another aspect there is provided a lighting system comprising a lighting unit,
the lighting system further comprising a lighting control circuit or a controller
as just described.
[0018] These and other aspects of the invention will be apparent from, and elucidated with
reference to, the embodiments described hereinafter.
Brief description of Drawings
[0019] Embodiments of the invention will be described, by way of example only, with reference
to the drawings, in which
Figure 1 illustrates methods according embodiments of the invention;
Figure 2 shows the dimmer current according to embodiments of the invention;
Figure 3 is a block diagram of a power management system which illustrates embodiments
of the invention
Figure 4 is a block diagram of a control block for use in embodiments of the invention;
Figure 5 illustrates waveforms and a timing diagram associated with a controller operable
in according with a leading edge phase-cut AC supply;
Figure 6 illustrates waveforms and a timing diagram associated with a controller operable
in according with a trailing edge phase-cut AC supply;
Figure 7 is a schematic circuit diagram of a conventional circuit for a leading edge
dimmer;
Figure 8 is a schematic circuit diagram of a circuit for a leading edge dimmer in
which the load can be disconnected from the dimmer;
Figure 9 shows simulated waveforms of a dimmer circuit according to embodiments in
which the first interval is synchronised with a mains zero-crossing;
Figure 10 shows simulated waveforms of a dimmer circuit according to embodiments in
which the first interval is not synchronised with a mains zero-crossing;
Figure 11 shows simulated waveforms of a dimmer circuit according to embodiments in
which the first interval is well synchronised with a mains zero-crossing, but in which
a proper firing mode is restored, and
Figure 12 shows a block diagram of a controller configured to restore a proper firing
mode.
[0020] It should be noted that the Figures are diagrammatic and not drawn to scale. Relative
dimensions and proportions of parts of these Figures have been shown exaggerated or
reduced in size, for the sake of clarity and convenience in the drawings. The same
reference signs are generally used to refer to corresponding or similar feature in
modified and different embodiments
Detailed description of embodiments
[0021] Embodiments of the invention are illustrated in figure 1: figure 1 shows, plotted
against time t, at 100, energy drawn from a generally sinusoidal mains power supply,
which is input into a phase-cut dimmer. In figure 1 the phase-cut dimmer is a leading-edge
dimmer. The dimmer is set to be heavily dimmed, that is to say, the dimmer switches
on only towards the end of each mains half-cycle. For the first part 106 of the mains
half-cycle, the dimmer is switched off, and does not supply any energy and so no energy
is transferred; during the last part108 of the mains half-cycle, the dimmer is switched
on and can transfer energy to a load.
[0022] This figure also shows, at 110, the energy which is delivered to a load. As can be
seen from plot 112, energy is continuously supplied to the load, in this example;
however, in other embodiments, such as that shown schematically at 114, energy need
not be supplied continuously: it may only be required intermittently.
[0023] If the power required by the load is very low, then the energy required by the load
over the mains half-cycle is also very low: thus, unless the conversion means itself
consumes significant energy, the energy required to be supplied from the mains during
the dimmer-on part 108 is also low, and thus the power during the dimmer-on part 108
may also be low.
[0024] As has already been discussed, if the power demanded from the dimmer is too low,
this may result in incorrect operation of the dimmer and in particular the dimmer
may fail to trigger. This problem is overcome, according to embodiments of the invention,
as shown in figure 1 by requiring the energy supplied during the dimmer-on the part
of the half-cycle, to be sufficient to power the load for one or more
additional half-cycles, during which additional half-cycles, the dimmer does not provide energy
for the load: in the illustration shown in figure 1, the dimmer is turned on during
the dimmer-on parts 104 of two consecutive half-cycles shown in the first interval
120, and then is NOT turned on during the subsequent four half-cycles shown at 130.
In this case, the quantum of energy drawn from the mains during each dimmer-on part
104 must be sufficient to supply energy to the load for three half-cycles (since 2
dimmer-on parts together supply the energy for both those two half-cycles and the
following four half-cycles). The power drawn from the mains during each dimmer-on
part 104 is thus three times as large as it would have been if the dimmer were made
to trigger for every half-cycle. The relative lengths of the first interval 120 and
the second interval 130 may be chosen so as to provide that the dimmer has to draw
sufficient power during each dimmer-on part such that correct triggering operation
occurs. This will in general depend on the particular application, and may or may
not be known before the system is installed. It will, generally, depend on the characteristics
of the specific type of dimmer used, and the level of dimming applied.
[0025] A simulated plot of dimmer output current over several half-cycles, for another embodiment,
is shown in figure 2. Figure 2 shows, at 210, a first set of three half-cycles 220
comprising a first interval, during which the dimmer operates in a conventional manner,
followed by a set of four half-cycles at 230 comprising a second interval during which
the dimmer remains off. At the end of the set of four half-cycles, a further set of
three half-cycles, during which the dimmer operates, commences. The group 240 of 7
half-cycles forms a "sub-cycle", which term will be considered in more detail below.
[0026] As shown in figure 2, the conduction angle 250 of the dimmer may generally be less
than the complete half-cycle 220. Thus the dimmer only conducts for a part of each
of the first three half-cycles. In other words, power is only drawn from the mains
over three parts of a first interval, which first interval comprises the first three
mains half-cycles. It will be noted that in figure 2 the dimmer is dimmed less than
in figure 1; in both cases a leading-edge dimmer is shown, although the invention
is not limited thereto. Similarly to the embodiment shown in figure 1, although not
shown in figure 2, the power is supplied to the load during at least one part of the
second interval, which second interval is the set of four half-cycles 230.
[0027] Figure 3 shows a block diagram of a system configured to manage supply to a load,
according to embodiments of the invention. The figure shows a dimmer 302 which is
connected to a dimmer load 304. The dimmer load comprises a load 306 which consumes
a certain power, for example a CFL (compact fluorescent lamp) driver stage. The dimmer
load 304 further comprises a switchable converter 308. The switchable converter 308
draws energy from the dimmer and, neglecting for the moment the energy consumed by
the switchable converter itself and other energy losses, delivers this energy to the
load. The dimmer load 304 further comprises a control block 310 which controls the
operation of the switchable converter 308. In particular the control block 310 only
allows the switchable converter 308 to draw power from the dimmer part of the time,
for instance during a specified time window of a sub-cycle (the term sub-cycle will
be defined in more detail hereinbelow). Neglecting losses, the energy drawn by the
switchable converter during the specified time window is equal to the energy required
by the load during the complete sub-cycle. Since the window is shorter than the sub-cycle,
the power drawn by the converter during this window is greater than the power of the
load, which power is supplied over the whole sub-cycle.
[0028] The term "sub-cycle" is used herein to describe an integral number of mains half-cycles.
Thus, for the sake of argument, the specified time window, corresponding to the first
interval may be 2 mains half-cycles, and the sub-cycle may be 6 mains half-cycles
if the first interval is followed by 4 half-cycles during which the dimmer does not
conduct at all. Then, in the case that the dimmer is fully on (that is to say there
is no phase-cutting at all and the mains supply is passed directly to the dimmer load),
the switchable converter would draw energy from the mains for two half-cycles, but
supply this energy over all 6 half-cycles: during the two half-cycles the switch mode
converter draws three times the power from the dimmer than it would were it to be
continuously drawing energy from the dimmer. The skilled person will appreciate, of
course, that the invention will generally be used where the dimmer is not fully on,
but is in a heavily dimmed state: the power drawn by the switchable converter during
the dimmer-on interval will then be significantly higher than it would be were the
dimmer always on; however, the increase in drawn power (by a factor of the sub-cycle
time divided by the window time, neglecting losses) still holds, for this " window-controlled
sub-cycle" operation. Although "sub-cycle" describes an integral number of mains half-cycles,
the first and second intervals discussed hereunder need not total to an integral number
of mains half-cycles, but may total to a non-intragral number of mains half-cycles.
In that case, there may be a delay between the end of a second interval and the start
of a next subsequent first interval. Such a delay may be useful in order that the
next subsequent first interval commences at a zero-crossing of the mains supply.
[0029] A non-limiting example of a switchable converter which may be used according to embodiments
of the invention is a PFC (power factor converter). For applications which include
a PFC stage, it is possible to switch the PFC on, that is to say switch it to an active
switching state, during the specified time window, and switch it off, that is to say
to an inactive state, outside of the window.
[0030] The skilled person would appreciate that, since the PFC stage is supplying energy
only during part of the sub-cycle, whilst the load, such as a CFL lamp or a LED lamp,
requires power to be supplied over the complete sub-cycle there needs to be some energy
buffer such as an intermediate bus capacitor, inside the application. As shown in
figure 3, the energy buffer may be inside the load 306 or the switchable converter
308 or may be a separate block within the connection between the load and the switchable
converter and shown as arrow 312.
[0031] The inventors have also appreciated that the switchable converter 308 does not necessarily
have to convert power during the complete conduction angle as set by the dimmer. For
instance it may be provided that the switchable converter converts power only during
part of a conduction angle, and then does not conduct for the whole of one or more
subsequent conduction angles. This will be considered in more detail in relation to
the non-limiting example of smart lighting on stand-by, below.
[0032] The dimmer itself may now be considered to be operating as a "slave" rather than
as a "master": the possibility for more flexibility in the management of the control
of the power arises. The function of the switchable converter is then twofold: firstly
to deliver the proper average power (over time) in order to supply the requirements
of the load; and secondly, to draw power from the dimmer, across the window, in such
a way that the dimmer can properly operate. In this context, proper operation means
that the switching element in the dimmer, such as a triac, is loaded by a sufficiently
high current to maintain it in and on-state once it has been fired. Moreover, it is
not necessary that power is supplied continuously to the load; in some embodiments
the load may only require intermittent power. Thus delivering the proper average power
over time in order to supply the requirements of the load, may include supplying power
at a variable level or even intermittently.
[0033] Figure 4 shows an example of a control block 310. Control block 310 includes a zero-crossing
generation block 410, which enables the control to determine the start (or end) of
the mains half-cycle, so as to ensure that the control remains in synchronisation
with the mains. The zero-crossing generation block 410 includes dv/dt detection 412,
zero-crossing detection 414 and a prediction block 416.
[0034] The zero-crossing generation block 410 takes as input the difference (d1-d2) between
line voltage d1 and the dimmer output d2. Assuming that the capacitor across the dimmer
output dominates, almost the complete amplitude of the mains is present at the inlets
(d1,d2) when the dimmer is off. The signal dVin/dt gives the steepness of the mains
line voltage d1, and can be sued to determine triggering event.
[0035] In the case that the dimmer does not fire (as will be discussed in more detail below)
this will be detected. This is shown as "no firing" in figure 4. When the dimmer does
not fire - that is to say, during the second interval, during which power is not drawn
from the mains, but is still supplied to the load - the zero-crossing cannot (in general)
be detected, so a zero-crossing prediction may have to be made, as shown by block
416.
[0036] Waveforms relevant to this control are shown at figure 5 for a leading edge dimmer,
and at figure 6 for a trailing edge dimmer respectively. The figures show d1-d2= Vin
(at 510 and 610 respectively), dVin/dt at 520 and 620 respectively, detected zero-crossings
at 530 and 630 respectively, and finally predicted zero-crossings (at 540 and 640).
As is shown in the figures, the zero-crossings can be directly detected only around
the first interval (that is to say, when the dimmer is conducting during at least
a part of the half-cycle), or end of each active cycle, provided that the (bleeder)
current is sufficient to prevent the triac from extinguishing before the mains voltage
zero crossing.
[0037] During the second interval (that is to say, the half-cycles where the dimmer does
not conduct at all), the zero-crossings cannot be directly detected, but are predicted
by means of the prediction block 416. Thus the output of the prediction block is a
continuous stream of zero-crossings, which continues even when no mains can be detected.
The absence of a steep dv/dt pulse can be used as indication that the dimmer triac
was not fired.
[0038] It will be immediately apparent to the skilled person, that there are several ways
to implement the prediction mechanism. For example, and without limitation, the prediction
block may extrapolate zero-crossings based on one or more sensed zero-crossings and
time information. If an accurate timing is present, such as a quartz crystal that
is often a basic part of a microcontroller system, there are only two zero-crossings
needed to predict the next ones. In cases in which the mains frequency is also known,
a single zero-crossing may be sufficient to predict the later zero-crossings.
[0039] In some embodiments, ensuring synchronisation of the controller with the phase of
the mains voltage may be necessary, in order to prevent a disturbance of the firing
network of the dimmer.
[0040] Triac dimmers typically use a firing network, often including a diac and an RC network.
A basic diagram of such a triac dimmer including a conventional firing network is
shown in Figure 7. The circuit shows triac T1, connected in series with an EMI-suppressing
coil L1, between input voltage V1 and ground in parallel with a smoothing capacitor
C2. The gate of the triac is supplied through diac X1. A resistor R2 is generally
provided, connected between gate of T1 and ground, in order to prevent unwanted switch-on
of the triac T1. The input to diac X1 is connected between V1 and ground, through
the RC network R1 and C1. R1 is either the dimmer potentiometer itself, or is adjustable
by means of the dimmer switch. As long as the triac conducts, the firing network R1,
C1 is supplied only to a minimal extent, due to the small voltage drop across the
triac, which is effectively being zero. When the triac turns off, which normally occurs
around the zero-crossing of the mains voltage, the triggering network starts charging
C1, starting at a voltage approximately zero or relative close to zero. This means
that the firing angle of the next cycle is almost completely determined by the mains
voltage shape after the zero-crossing. It should be noted that, in practice, the firing
angle is dependent on history to some extent, since some energy may remain in the
capacitor C1 after firing the triac, depending on the properties of the trigger device
X1.
[0041] Figure 8 shows schematic of a circuit that consumes zero, or almost zero, power,
when the dimmer is not conducting. In this circuit, a triac dimmer is connected to
an AC mains (V2) and loaded with a resistor R3 that can be switched off by, for instance,
a voltage programmable resistor (X3). In other embodiments, a switch may be used,
or a PFC (power factor control) stage may be switched on, in order to provide the
loading. The resistor X3 is equal to the voltage between Rp and Rm. The load may thus
be switched to a mode where it consumes almost no power from the mains during the
off window. In this mode, the zero-crossings of the mains cannot always be detected
because the voltage 510,610 depends on the actual capacitance present at both dimmer
output (that it, the voltage across C2) and input of the load (represented by R3,
X3 in fig 8). In the circuit of Figure 8, which results in the signals shown in figure
5, the ideal situation is drawn: no capacitance at all is present at input of the
load, while the load is switched to the high ohmic mode at the zero-crossing of the
mains. C2 is then held at its last value of 0V (immediately after the dimmer turns
off). This means that the full mains voltage remains present at the input of the load.
However, in the case that a capacitor (with an undefined impedance) is present at
the input of the load, or in the case that the load is switched to the high-ohmic
mode at a moment other than at the zero-crossing of the mains, the phase relation
between mains voltage and voltage at the input of the load, becomes uncertain, while
the residual voltage at C2 disturbs the DC component at input of the load.
[0042] When the triac is conducting, the voltage across C1 (and thus across diac X1) remains
at a low value until the zero-crossing of the mains, because the voltage across the
conducting triac is low, keeping the firing network discharged. The connection between
the dimmer and the load is interrupted at the zero-crossing of the mains. By switching
the power off at the zero-crossing, the input of the firing network becomes high ohmic,
preventing C1 from being charged provided that C2 is large compared to the input capacitance
of the application (parallel to R3, not shown). When the connection between the dimmer
and the load is re-established close to a zero-crossing, C1 is charged similar to
the situation in which there was no power switch off; in other words, the firing angle
during the interval where power is taken is not significantly changed compared with
the situation where this power is continuously taken.
[0043] As already indicated it may be desirably to detect the mains zero-crossing, or to
predict this when it cannot be directly detected. This will be illustrated having
regard to figures 9 and 10, which show the effects of good, and poor, synchronisation
respectively. Figures 9 and 10 show, against time on the x-axis or abscissa, plots
of the current through R3 at 910 and 1010; the voltage across the input terminals
of the programmable switch X3 at 920 and 1020; the input mains voltage at 930 and
1030; and the voltage Vdiac across the diac at 940 and 1040, in Figures 9 and 10,
respectively for a controller in which the power-supplying first interval is, and
is not, properly synchronized with the mains zero-crossing. In the example shown in
figure 9, the start of the first interval is synchronized close to the zero-crossing
of the mains (shown at about 12ms and 10ms respectively), whilst in figure 10 the
first interval is started at 6ms, which is significantly different from the 10ms position
of the zero-crossing. This latter situation results in charging of the firing network
starting before the zero-crossing and therefore Vdiac starts with a pre-biasing voltage
of the wrong sign, making it impossible to reach the trigger level of the diac before
the next zero-crossing and therefore no firing at all and disturbance of the dimming
process.
[0044] It would be necessary to increase the power level of the dimmer via adjusting the
potentiometer R
1 manually, to overcome this situation, unless preventative measures are taken. An
example of such a preventative measure is illustrated in figure 11, which shows plots
against time of the same currents and voltages, as well as a plot of the voltage at
the dimmer terminal, that is, the voltage V
T2 at terminal T2 of X3 in figure 8, at 1350. As in figure 10, between t=6ms and t=20ms,
the firing network operates in the wrong mode. At t=20ms, being a zero-crossing of
the mains voltage, the load is disconnected. The result is that the voltage at the
dimmer terminal V
T2 remains 0 and in this way C1 is prevented from being charged to the opposite polarity.
If the load is now connected at the next zero-crossing, the polarity of the voltage
at C1 has the proper sign to be charged to the firing level. In this way the system
can be forced to the proper mode of operation of the firing network again. Therefore
the sequence of (a) disconnecting the load close to a zero-crossing of the mains voltage
when no firing angle is detected followed by; (b) connecting the load to the mains
at the next zero-crossing of the mains (or the Nth zero-crossing as an alternative,
N being an odd number) may ensure proper operation of the device.
[0045] As the mains voltage cannot be sensed while the triac is off and a load is connected
to the dimmer, it may be possible to use this method only if the zero-crossings can
be determined in another way. If the load is disconnected it is again possible to
sense the shape of the mains voltage and to lock the zero-crossing generation block
such that it predicts the zero-crossings, as discussed above. Generally, then, the
zero-crossing generation including predicting future zero-crossings is carried out
before the load is disconnected.
[0046] Figure 12 shows a block diagram of a control block according to an embodiment implementing
the above features: in this embodiment, the control block 310 include zero-crossing
generation block 410, together with logic 1210. A signal 'enable window' defines the
desired length of the window, during which the dimmer is able to supply power, that
is to say, it defines the first interval. Without limitation, the first interval may
be a single half-cycle, or may be multiple half-cycles. In other embodiments, the
first interval may be shorter than a single half-cycle. In particular in such other
embodiments, the first interval may be shorter than the conduction angle of the dimmer,
such that, in order to transfer the same energy as would be the case were the dimmer
to be conducting over the whole of its conduction window, it has to operated at a
higher power for the shorter first interval.
[0047] The logic block 1210 synchronizes the enable window with the zero-crossings of the
mains voltage in order to maintain proper operation of the firing network of the dimmer.
In some embodiments this block may also, when no firing is detected, disconnect the
load close to a zero-crossing of the mains voltage and reconnect the load to the dimmer
at the next, or a subsequent zero-crossing of the mains. The triac should then fire
according to the correct operation. In some embodiments, in case that no zero-crossing
signal is available, logic 1210 can be set to disconnect the load from the dimmer
for a few mains cycles in order to sense the zero-crossings and lock the zero-crossing
generation block, as discussed above.
[0048] Some embodiments of the invention may be used for instance to supply stand-by power
to a controller such as a smart lighting controller. In such an application, the controller
may only require a minimal level of power, sufficient only to ensure that the controller
"wakes up" when required. Such power may generally be supplied by a battery or capacitor.
However, when the charge in the battery or capacitor falls below a certain level,
it will require recharging. The recharging may be through the lighting dimmer and
may require only a small amount of energy. If the dimmer were to provide this energy
spread across the whole of one conduction angle, it may be that the power level would
be too low to trigger the dimming device (either a triac or transistor), particular
if the dimmer is set so as not to heavily dim - that is so the conduction angle is
a large part - or even all, of the half-cycle. In such a case, according to embodiments
of the invention, the first interval may be only a part of the conduction angle of
the dimmer. Since the energy is then drawn during only a shorter interval than the
conduction angle, the power level is thus higher than would be the case were the energy
transfer to occur over the complete conduction angle.
[0049] Other embodiments of the invention may also be used in applications such as smart
lighting as just discussed. The difference between the average power required by the
application, and the power required in order to correctly operate a dimmer, whether
triac-based, or transistor-based, may be even more pronounced: the light may be heavily
dimmed - for instance in response to a signal such as from a wireless remote control
- even when the dimmer is set for a high light level, and so would be expected to
be conducting during almost the complete mains cycle. In this situation the losses
associated with bleeder dissipation absent a method such as is disclosed in embodiments
above, might be even more than in a standard lighting application.
[0050] Although embodiments described above have been directed mainly to leading edge phase
cut mains supplies, the skilled person will appreciate that the invention is not limited
thereto; in particular, controllers for trailing edge phase cut AC supplies may fall
within the scope of the invention. Generally, the power level during conduction of
the dimmer switch - which typically in this case is a MOS transistor, should be maintained
at a sufficiently high level that the switch does not turn-off prematurely, before
the end of the conduction-angle (or, in the case of a window or first interval which
is smaller than the conduction angle, before the end of the window). Further, for
trailing edge dimmers, synchronisation with the mains zero crossing may be less critical,
provided only that the timing is sufficiently nearly synchronised that the window
does not completely miss the conduction angle (which could possibly be the case under
very heavily dimmed operation).
[0051] Further, the skilled person will appreciate that although the example embodiments
above have been described in relation at a phase-cut mains supply, the invention may
also extend to other AC supplies, such as, without limitation, a marine or aircraft-based
AC-supply, or an inverter-based supply.
[0052] From reading the present disclosure, other variations and modifications will be apparent
to the skilled person. Such variations and modifications may involve equivalent and
other features which are already known in the art of phase-cut dimmers, and which
may be used instead of, or in addition to, features already described herein.
[0053] Although embodiments above have been described in relation to phase-cut dimmers such
as are commonly used in lighting circuit, the skilled person will appreciate that
the invention is not limited thereto, but extend to other leading edge or trailing
edge phase-cut AC supplies designed for applications other than lighting, such as
power control for an electric fan by phase cut control.
[0054] It will be appreciated that, in order to provide a clear understanding of the invention,
in the above discussion a simplifying assumption has been made that the load current
through the triac is pure resistive, or at least completely in phase with the mains
voltage. The skilled person will be aware that in practice, some phase shift may occur,
and can readily derive the circuit behaviour of such non-resistive output loads. For
clarity, however, these effects are not discussed herein, since they are not of relevance
for the invention.
[0055] Although the appended claims are directed to particular combinations of features,
it should be understood that the scope of the disclosure of the present invention
also includes any novel feature or any novel combination of features disclosed herein
either explicitly or implicitly or any generalisation thereof, whether or not it relates
to the same invention as presently claimed in any claim and whether or not it mitigates
any or all of the same technical problems as does the present invention.
[0056] Features which are described in the context of separate embodiments may also be provided
in combination in a single embodiment. Conversely, various features which are, for
brevity, described in the context of a single embodiment, may also be provided separately
or in any suitable sub-combination.
[0057] The applicant hereby gives notice that new claims may be formulated to such features
and/or combinations of such features during the prosecution of the present application
or of any further application derived therefrom.
[0058] For the sake of completeness it is also stated that the term "comprising" does not
exclude other elements or steps, the term "a" or "an" does not exclude a plurality,
a single processor or other unit may fulfil the functions of several means recited
in the claims and reference signs in the claims shall not be construed as limiting
the scope of the claims.
1. A method of managing the supply of power to a load from a phase-cut AC supply over
a plurality of AC supply half-cycle periods, the method comprising:
- drawing energy from the phase-cut AC supply during at least one part of a first
interval, the first interval being at least part of at least one AC supply half-cycle,
- storing some of the energy and
- supplying the some of the energy to the load during a second interval being at least
one subsequent AC supply half-cycle,
- wherein the first and second intervals total to the plurality of AC supply half-cycle
periods.
2. The method of any preceding claim further comprising:
- setting a duration of at least one of the first interval and the second interval
such that the power drawn during the at least part of the first interval is sufficient
to enable triggering of the AC phase-cutting device.
3. The method of claim 1 or 2 wherein the first interval is an AC supply half-cycle and
the at least part of a first interval comprises a single window.
4. The method of claim 1 or 2 wherein the first interval is a plurality of AC supply
half-cycles, and the at least part of a first interval comprises a single window in
each of the plurality of AC supply half-cycles.
5. The method of claim 3 or 4 further comprising
- detecting a phase of the AC supply, and
- synchronising the or each window to the phase of the AC supply.
6. The method of claim 5 wherein
- detecting a phase of the AC supply comprises detecting a zero-crossing of the mains,
- the method further comprising predicting a further zero-crossing based on the detected
zero-crossing.
7. The method of any of claims 3 to 6, wherein the first and second interval total to
an odd-number of AC supply half-cycles.
8. The method of claim 1 or 2, wherein the at least one part of a first interval is one
part of a first interval and is shorter than a conduction angle of the phase-cut AC
supply.
9. A controller for supplying power to a load from a phase-cut AC supply over a plurality
of AC supply half-cycle periods, the controller being connectable to an energy store,
the controller being configured to:
- draw energy from the phase-cut AC supply during at least one part of a first interval,
the first interval being at least part of at least one AC supply half-cycle,
- store some of the energy in the energy store and
- supply the some of the energy to the load during a second interval being at least
one subsequent AC supply half-cycle,
- wherein the first and second interval total to the plurality of AC supply half-cycle
periods.
10. A controller according to claim 9, wherein the energy store is a capacitor.
11. A controller according to claim 9 or 10, further comprising a zero-crossing detection
unit.
12. A controller according to any of claims 9 to 11, further comprising a zero-crossing
prediction unit.
13. A load control circuit comprising a switched mode power converter and a controller
according to any of claims 9-12.
14. A load system comprising a load, the load system further comprising a load control
circuit as claimed in claim 13 or a controller as claimed in any of claims 9-12.
15. A lighting system comprising a lighting unit, the lighting system further comprising
a load control circuit as claimed in claim 13 or a controller as claimed in any of
claims 9-12.