This application is a continuation of U.S. Patent Application Serial No. 60/051,102, filed June 27, 1997.

This application relates in general to measurement and sensing of low power signals. More particularly, the invention relates to the sensing, amplification and measurement of a low power, light-based signal.

Figure 1 illustrates a circuit 100 of the prior art for amplifying a signal from a photo diode 130. The circuit of Figure 1 includes the photo diode 130 connected across the inputs of an operational amplifier 120. The positive input of the op amp 120 is tied to ground. A resistive load R 150 is coupled between the negative terminal and the out signal 110 of the op amp 120.

Notably, the feedback resistor R 150 has inherent thermal noise that can sometimes exceed the actual signal from the photo diode 130. The output from a resistive feedback amplifier such as circuit 100 is given in equation (1) below: $$V_{\mathit{out}}=-\mathit{i\; R}$$
where V_out is in volts, i is the input signal in amperes from a signal source (such as photo diode 130) and R is the feedback resistance (such as the resistor R 150) in ohms.

A component with resistance generates thermal noise with the following RMS values: $$V_{{\mathit{RMS}}_{\mathit{noise}}}=\sqrt{\mathit{4}\mathit{kTBR}}$$ $$I_{{\mathit{RMS}}_{\mathit{noise}}}=\sqrt{\mathit{4}\mathit{kT}\frac{\mathit{B}}{\mathit{R}}}$$
where V_{RMS noise} is in volts and I_{RMS noise} is in amperes and where k = 1.38 × 10^-23 J/°K (Boltzmann's constant), T is the absolute temperature in °K, B is the bandwidth in Hz and R is the resistance in ohms.

Therefore, when an application requires the amplification of a very low signal from a photo diode, the prior art resistive feedback amplifier 100 sometimes proves unuseful due to excessive noise, for example.

Figure 2 presents a circuit 200 of the art, designed to avoid this thermal noise problem. In Figure 2, the photo diode 130 remains coupled across the inputs of the op amp 120. In place of the resistive element R 150, a capacitor 220, coupled between the negative input and the output 210 of the op amp 120, serves as the feedback element. The source of a field-effect transistor (FET) 230 is coupled to the output 210 of the op amp 120 while the drain is coupled to the negative input of the op amp 120. The gate of the FET 230 serves as a Reset signal 240.

The use of the capacitor 220 as the feedback element eliminates the noise problem of the circuit 100.

The output from an integrator such as the circuit 200 is given in equation (4) below: $$V_{\mathit{out}}=-i\frac{t}{C}$$
where i is the input signal from a signal source (such as photo diode 130) in amperes, t is the time from reset to reading in seconds and C is the feedback capacitance (of capacitor 220, for example) in farads.

Figure 3 illustrates the timing of the operation of the circuit 200 of Figure 2. A control circuit (not shown) typically resets the integrator 200 (by means of the Reset signal 240) at twice the rate of the signal bandwidth. Just prior to each of these resets, the control circuit reads the out signal 210 and extracts the true signal.

The use of the semiconductor switch 230, however, creates its own problems in the circuit 200. The charge transfer itself from the Reset signal 240 during the resetting of the integrator 200 induces noise. To avoid this problem, the control circuit reads the out signal 210 right after releasing the reset switch 240. The control circuit then subtracts this reading from the final reading.

The noise of the photo diode 130 and op amp 120 nonetheless affect the two-reading scheme used with the circuit 200 up to the bandwidth of the system. The system bandwidth has to be much higher than the signal bandwidth in order not to distort the integration curves.

Accordingly, there is a need for a circuit for an improved detector of low levels of light without the thermal noise and other problems described above. These and other goals of the invention will be readily apparent to one of ordinary skill in the art on the reading of the background above and the invention description below.

Document US-A-5 307 145 defines a process and apparatus for measuring small quantities of light.

Herein is disclosed a method and apparatus for measuring very low power signals such as low power light signals, including integrating a signal from a signal source such as a photo diode, an avalanche photo diode, a photomultiplier tube or the like, digitally sampling the integrator output multiple times during each integration period, fitting a curve to the multiple digitized readings to calculate the integration slope for each integration period and determining the original signal from the calculated integration slope.

According to an aspect of the invention, an apparatus for use in measuring low power signals is provided, the apparatus comprising: all the characteristics of claim1. According to another aspect a method comprising all the steps recited in claim 14 is defined.

Additional embodiments are defined in dependent claims.

Reference to the remaining portions of the specification, including the drawings and claims, will realize other features and advantages of the present invention. Further features and advantages of the present invention, as well as the structure and operation of various embodiments of the present invention, are described in detail below with respect to the accompanying drawings. In the drawings, like reference numbers indicate identical or functionally similar elements.

• Figure 1 illustrates a circuit of the prior art for amplifying a signal from a photo diode;
• Figure 2 presents a circuit of the prior art, designed to avoid the thermal noise problem;
• Figure 3 illustrates the timing of the operation of the circuit of Figure 2;
• Figure 4 illustrates a circuit 400 according to the invention;
• Figure 5 illustrates the timing of the operation of the circuit 400 of Figure 4;
• Figure 6 illustrates the overall operation of the circuit of Figure 4; and
• Figure 7 illustrates an example of a microfluidic device for use with certain aspects of the present invention.

In preferred aspects, the method and apparatus of the instant invention are used in the detection of light-based signals from analytical systems employing optical detection in microscale fluidic channels. Examples include, e.g., fused silica capillary systems, i.e., CE, as well as microfluidic devices and systems that incorporate microscale channels such as microfluidic channels. Such systems are generally described in U.S. Patent Application Nos. 08/845,754 (Attorney Docket No. 100/01000, filed April 25, 1997), 08/881,696 (Attorney Docket No. 17646-000420, filed June 24, 1997), a continuation-in-part of U.S. Patent Application No. 08/761,575 (filed December 6, 1996), and 60/049,413 (Attorney Docket No. 17646-003600), filed June 9, 1997.

A "microfluidic" channel is a channel (groove, depression, tube, etc.) which is adapted to handle small volumes of fluid. In a typical embodiment, the channel is a tube, channel or conduit having at least one subsection with at least one cross-sectional dimension of between about 0.1 µm and 500 µm, and typically less than 100µm; ordinarily, the channel is closed over a significant portion of its length, having top, bottom and side surfaces. In operation, materials that are being analyzed, e.g., subjected to optical analysis for light based signals, in these microscale fluidic systems, are transported along the microscale fluid channels, past a detection point, where a detectable signal indicative of the presence or absence of some material or condition, is measured. In the case of light based detection systems, the signals within these channels typically result from the presence of light emitting substances therein, e.g., fluorescent or chemiluminescent materials, that are used as indicators of the presence of absence of some material or condition. Because microscale channels have extremely small dimensions, the amount of signal typically available for detection within such channels is also extremely small. For example, in the microfluidic systems for which the present invention is particularly useful, the power levels of signals from a detection region in a microfluidic channel are typically on the order of about 0.1pW to about 10pW.

As noted above, in microscale analytical systems, a signal bearing material is transported along the microscale channel and past a detection point. Typically, transporting materials within these systems may be carried out by any of a variety of methods. For example, such material transport is optionally carried out through the application of pressures to the materials within the channels, through the incorporation of microscale mechanical pumps, or through the application of electric fields, to move materials through the channels.

In preferred aspects, the above microfluidic systems use electrokinetic transport systems for moving material within the microfluidic channels. As used herein, "electrokinetic material transport systems" include systems which transport and direct materials within an interconnected channel and/or chamber containing structure, through the application of electrical fields to the materials, thereby causing material movement through and among the channel and/or chambers (i.e., cations will move toward the negative electrode, while anions will move toward the positive electrode). Such electrokinetic material transport and direction systems include those systems that rely upon the electrophoretic mobility of charged species within the electric field applied to the structure. Such systems are more particularly referred to as electrophoretic material transport systems. Other electrokinetic material direction and transport systems rely upon the electroosmotic flow of fluid and material within a channel or chamber structure which results from the application of an electric field across such structures. In brief, when a fluid is placed into a channel which has a surface bearing charged functional groups, e.g., hydroxyl groups in etched glass channels or glass microcapillaries, those groups can ionize. In the case of hydroxyl functional groups, this ionization (e.g., at neutral pH), results in the release of protons from the surface and into the fluid, creating a concentration of protons at near the fluid/surface interface, or a positively charged sheath surrounding the bulk fluid in the channel. Application of a voltage gradient across the length of the channel will cause the proton sheath to move in the direction of the voltage drop (i.e., toward the negative electrode).

Figure 7 depicts an example of a microfluidic device for use with certain aspects of the present invention. As shown, the device 300 includes a body structure 302 which has an integrated channel network 304 disposed therein. The body structure 302 includes a plurality of reservoirs 306-328, disposed therein, for holding reagents, sample materials, and the like. Also included is buffer reservoir 330, as well as waste reservoirs 332, 334 and 336. The reagents, samples, etc. are transported from their respective reservoirs, either separately or together with other reagents from other reservoirs into a main channel 338, and along main channel 338 toward waste reservoir 336, past detection zone or window 340. Detection window 340 is typically transparent, and may be comprised of a transparent region of the body structure, or a separate transparent window fabricated into the body structure. Typically, the body structure is itself fabricated from a transparent material, e.g., glass or transparent polymers, thereby obviating the need for a separate transparent region to define the detection window. Microfluidic devices of the sort described above are useful in performing a variety of analyses, such as electrophoretic separation of macromolecules, e.g., nucleic acids, proteins, etc. (see U.S. Application No. 08/845,754, filed April 25, 1997, and previously incorporated herein by reference), high throughput screening assays, e.g., in pharmaceutical discovery, and diagnostics, e.g., immunoassays (see, e.g., Published International Application No. WO 98/00231).

In one embodiment, a signal source is located proximal detection window 340 for detecting low power, light-based signals from the detection region. The signal source is optionally selected from a number of different types of light detectors, i.e., photo diodes, avalanche photo diodes, photomultiplier tubes (PMTs) and the like. In preferred aspects, a photo diode is used. Figure 4 illustrates a circuit 400 for amplifying a signal from a photo diode 130 according to the invention. In Figure 4, the photo diode 130 is coupled across the inputs of an op amp 120. A capacitor 220, coupled between the negative input and the output 210 of the op amp 120, serves as the feedback element. The source of a field-effect transistor (FET) 230 is coupled to the output 210 of the op amp 120 while the drain is coupled to the negative input of the op amp 120. The gate of the FET 230 is connected to Reset signal 440.

The input of a low-pass filter 410 is coupled to the output signal 210. The output of the low-pass filter 410 is coupled to the analog input of an analog-to-digital converter 420. Finally, a microprocessor 430 receives as input the digitized output signal 450 of the analog-to-digital converter 420.

Figure 6 illustrates the overall operation of the circuit 400. The circuit 400 receives and integrates a signal from a photo diode and resets the integrator, step 610. The circuit 400 then filters out the higher frequencies in the integrated signal, step 620. Next, the circuit 400 converts the analog filtered and integrated signal to digital samples, step 630. Finally, the circuit 400 calculates the integration slope for the photo diode signal by fitting a curve to the digitized samples, step 640. With the calculated slopes, the circuit 400 is better able to determine the original noise-less signal from the photo diode.

Figure 5 illustrates the timing of operation of the circuit 400 of Figure 4. In contrast to the prior art circuit 200 which just takes two readings for each integration period, the circuit 400 takes many readings 530 for each integration period. In preferred aspects, analog-to-digital converter 420 samples the integrator output more than two times, preferably more than ten times, still more preferably more than one-hundred times, in many cases more that five hundred and even more than one-thousand times.

Also in contrast to the prior art circuit 200, the circuit 400 applies a more sophisticated curve-calculation routine to the per-period sample readings to generate the per-period calculated slopes 510 and 520. The curve calculation filters away overlying noise. In this way, the circuit 400 decreases the noise contribution from the photo diode 130 and the op amp 120 near to what is included in the signal bandwidth.

The frequency of the Reset signal 440, f_Reset, is fast enough to allow detection of the fastest signal necessary, f_Signal. In one embodiment, f_Reset is approximately twice f_Signal.

The frequency of the low-pass filter 410, f_Low-Pass, is fast enough that the integration curves do not become significantly disturbed. f_Low-Pass is dependent on signal distortion specifications. In one embodiment, f_Low-pass is approximately ten times f_Reset.

To best filter noise, in one embodiment, the sample frequency, f_sample, is at least twice f_Low-pass.

The microprocessor 430 uses any of the numerous curve-fitting algorithms known in the art to calculate the slope of each integration period. Least-squares curve fitting is but one example of these algorithms. Any curve-fitting algorithm that filters away overlaid noise can be used. For example, the curve-fitting algorithm can be: 0.5 × f_Reset×(First Readings - Last Readings), where "First Readings" are the first half of the samples taken within an integration period and "Last Readings" are the second half of the samples taken within an integration period.

The circuit 400 filters both voltage noise and current noise from the op amp 120 and photo diode 130 close to the theoretical value included in the signal band. Noise can be almost totally ignored.

The noise in the measurement is affected by the amount of noise at the negative input of the integrating op amp 120. Any component will generate noise as described in equations (2) and (3) above. Therefore, in a preferred embodiment, all components connected to the negative input of op amp 120 have very high resistance. Also, op amp 120 preferably has low noise parameters.

The embodiments described herein are by way of example and not limitation. Modifications to the invention as described will be readily apparent to one of ordinary skill in the art. For example, while the photo diode 130 is described as a signal source above, it is understood that any sensor giving voltage or current signals or any source of readings convertible to current or voltage readings can be the signal source. (Of course, if the signal source is a voltage output, a resistor converts it to a current output adaptable to the circuit described.) Still further, while a FET device 230 is described as the resetting mechanism, other devices which have high resistance when not asserting the Reset signal 440 can be used. For example, the resetting mechanism can be an opto-activated FET or opto-activated diode or relay or another kind of transistor.

Of course, the program text for such software as is herein disclosed can exist in its static form on a magnetic, optical or other disk, on magnetic tape or other medium requiring media movement for storage and/or retrieval, in ROM, in RAM or other integrated circuit, or in another data storage medium. That data storage medium may be integral to or insertable into a computer system.